Smith Chart - 1 Transmission Lines and Waveguides 4. The Smith Chart by Nannapaneni Narayana Rao.
Lecture 6 Lossy Transmission Lines and the Smith Chart
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Transcript of Lecture 6 Lossy Transmission Lines and the Smith Chart
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8/2/2019 Lecture 6 Lossy Transmission Lines and the Smith Chart
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EECS 117
Lecture 6: Lossy Transmission Lines and the SmithChart
Prof. Niknejad
University of California, Berkeley
University of California, Berkeley EECS 117 Lecture 6 p. 1/
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Dispersionless Line
To find the conditions for the transmission line to bedispersionless in terms of the R, L, C, G, expand
=
(jL + R)(jC + G)
=
(j)2LC(1 +
R
jL+
G
jC+
RG
(j)2LC)
=
(j)2LC
Suppose that R/L = G/Cand simplify the
term
= 1 +2R
jL+
R2
(j)2L2
University of California, Berkeley EECS 117 Lecture 6 p. 2/
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Dispersionless Line (II)
For R/L = G/C the propagation constant simplifies
=
1 +
R
jL2
= jLC1 + RjLBreaking into real and imaginary components
= RCLjLC= + j
The attenauation constant is independent of
frequency. For low loss lines, RZ0 The propagation constant is a linear function of
frequencyUniversity of California, Berkeley EECS 117 Lecture 6 p. 3/
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Lossy Transmission Line Attenuation
The power delivered into the line at a point z is nownon-constant and decaying exponentially
Pav(z) = 12 (v(z)i(z)) = |v
+
|2
2|Z0|2 e2z (Z0)
For instance, if = .01m1, then a transmission line oflength = 10m will attenuate the signal by 10 log(e2) or
2 dB. At = 100m will attenuate the signal by 10 log(e2)or 20 dB.
University of California, Berkeley EECS 117 Lecture 6 p. 4/
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Lossy Transmission Line Impedance
Using the same methods to calculate the impedance forthe low-loss line, we arrive at the following linevoltage/current
v(z) = v+ez(1 + Le2z) = v+ez(1 + L(z))
i(z) =v+
Z0 ez
(1 L(z))Where L(z) is the complex reflection coefficient atposition z and the load reflection coefficient is unalteredfrom before
The input impedance is therefore
Zin(z) = Z0 ez + Lezez Lez
University of California, Berkeley EECS 117 Lecture 6 p. 5/
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Lossy T-Line Impedance (cont)
Substituting the value of L we arrive at a similarequation (now a hyperbolic tangent)
Zin() = Z0ZL + Z0 tanh()Z0 + ZL tanh()
For a short line, if
1, we may safely assume that
Zin() = Z0 tanh() Z0
Recall that Z0= Z/YZYAs expected, input impedance is therefore the seriesimpedance of the line (where R = R and L = L)
Zin() = Z = R + jLUniversity of California, Berkeley EECS 117 Lecture 6 p. 6/
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Review of Resonance (I)
Wed like to find the impedance of a series resonator
near resonance Z() = jL + 1jC + R
Recall the definition of the circuit Q
Q = 0time average energy stored
energy lost per cycle
For a series resonator, Q = 0L/R. For a smallfrequency shift from resonance 0
Z(0 + ) = j0L + jL +1
j0C
1
1 + 0
+ R
University of California, Berkeley EECS 117 Lecture 6 p. 7/
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Review of Resonance (II)
Which can be simplified using the fact that 0L =1
0C
Z(0 + ) = j2L + R
Using the definition of Q
Z(0 + ) = R
1 + j2Q
0
For a parallel line, the same formula applies to the
admittance
Y(0 + ) = G
1 + j2Q
0
Where Q = 0C/GUniversity of California, Berkeley EECS 117 Lecture 6 p. 8/
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/2 T-Line Resonators (Series)
A shorted transmission line of length has inputimpedance of Zin = Z0 tanh()
For a low-loss line, Z0 is almost real
Expanding the tanh term into real and imaginary parts
tanh(+j) =
sinh(2)
cos(2) + cosh(2) +
j sin(2)
cos(2) + cosh(2)
Since 0f0 = c and = 0/2 (near the resonantfrequency), we have = 2/ = 2f/c = + 2f/c = + /0
If the lines are low loss, then 1
University of California, Berkeley EECS 117 Lecture 6 p. 9/
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/2 Series Resonance
Simplifying the above relation we come to
Zin = Z0 + j 0
The above form for the input impedance of the seriesresonant T-line has the same form as that of the series
LRC circuit
We can define equivalent elements
Req = Z0 = Z0/2
Leq =
Z0
20 Ceq =
2
Z00
University of California, Berkeley EECS 117 Lecture 6 p. 10/
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/2 Series Resonance Q
The equivalent Q factor is given by
Q =1
0ReqCeq=
0=
0
2
For a low-loss line, this Q factor can be made very large.A good T-line might have a Q of 1000 or 10,000 or more
Its difficult to build a lumped circuit resonator with sucha high Q factor
University of California, Berkeley EECS 117 Lecture 6 p. 11/
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/4 T-Line Resonators (Parallel)
For a short-circuited /4 line
Zin = Z0 tanh( + j) = Z0tanh + j tan
1 + j tan tanh
Multiply numerator and denominator by j cot
Zin = Z01j tanh cot tanhj cot
For = /4 at = 0 and = 0 +
=0
v+
v=
2+
20
University of California, Berkeley EECS 117 Lecture 6 p. 12/
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/4 T-Line Resonators (Parallel)
So cot = tan20
20
and tanh
Zin = Z0
1 + j/20
+ j/20 Z0
+ j/20
This has the same form for a parallel resonant RLCcircuit
Zin =1
1/R + 2jC
The equivalent circuit elements are
Req =Z0
Ceq =
40Z0Leq =
1
20Ceq
University of California, Berkeley EECS 117 Lecture 6 p. 13/
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/4 T-Line Resonators Q Factor
The quality factor is thus
Q = 0RC=
4
=
2
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The Smith Chart
The Smith Chart is simply a graphical calculator forcomputing impedance as a function of reflectioncoefficient z = f()
More importantly, many problems can be easilyvisualized with the Smith Chart
This visualization leads to a insight about the behavior
of transmission lines
All the knowledge is coherently and compactlyrepresented by the Smith Chart
Why else study the Smith Chart? Its beautiful!
There are deep mathematical connections in the SmithChart. Its the tip of the iceberg! Study complex analysis
to learn more.
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Generalized Reflection Coefficient
In sinusoidal steady-state, the voltage on the line is aT-line
v(z) = v+
(z) + v
(z) = V+
(ez
+ Lez
)
Recall that we can define the reflection coefficientanywhere by taking the ratio of the reflected wave to the
forward wave
(z) =v(z)
v+(z)=
Lez
ez= Le
2z
Therefore the impedance on the line ...
Z(z) =v+ez(1 + Le
2z)v+
Z0ez(1 Le2z)
University of California, Berkeley EECS 117 Lecture 6 p. 17/
N li d I d
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Normalized Impedance
...can be expressed in terms of (z)
Z(z) = Z01 + (z)
1 (z)It is extremely fruitful to work with normalizedimpedance values z = Z/Z0
z(z) =Z(z)
Z0=
1 + (z)
1 (z)Let the normalized impedance be written as z = r + jx(note small case)
The reflection coefficient is normalized by default
since for passive loads || 1. Let = u + jvUniversity of California, Berkeley EECS 117 Lecture 6 p. 18/
Di ti f th T f ti
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Dissection of the Transformation
Now simply equate the and components in theabove equaiton
r + jx = (1 + u) + jv(1 u)jv = ((1 + u + jv)(1 u + jv)(1 u)2 + v2
To obtain the relationship between the (r,x) plane and
the (u,v) plane
r =1 u2 v2
(1 u)2 + v2
x =v(1 u) + v(1 + u)
(1 u)2 + v2
The above equations can be simplified and put into anice formUniversity of California, Berkeley EECS 117 Lecture 6 p. 19/
C l ti Y S
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Completing Your Squares...
If you remember your high school algebra, you canderive the following equivalent equations
u r
1 + r
2+ v2 = 1
(1 + r)2
(u 1)2 + v 1x2
= 1x2
These are circles in the (u,v) plane! Circles are good!
We see that vertical and horizontal lines in the (r,x)plane (complex impedance plane) are transformed tocircles in the (u,v) plane (complex reflection coefficient)
University of California, Berkeley EECS 117 Lecture 6 p. 20/
R i t T f ti
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Resistance Transformations
u
r=0
r=0
.5
r=
1
r
=
2
v
r=.5 r=1 r=2r=0
r
r = 0 maps to u2 + v2 = 1 (unit circle)
r = 1 maps to (u 1/2)2 + v2 = (1/2)2 (matched realpart)r = .5 maps to (u 1/3)2 + v2 = (2/3)2 (load R less thanZ0)
r = 2 maps to (u 2/3)2 + v2 = (1/3)2 (load R greaterthan Z0)
University of California, Berkeley EECS 117 Lecture 6 p. 21/
R t T f ti
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Reactance Transformations
x
r
u
x=.5
x
=
1x=2
x=-.5
x
=
-1
x=-2
v
x= 1
x= 2
x= -1
x= -2
x= 0
x = 1 maps to (u 1)2 + (v 1)2 = 1x = 2 maps to (u 1)2 + (v 1/2)2 = (1/2)2
x = 1/2 maps to (u 1)2 + (v 2)2 = 22Inductive reactance maps to upper half of unit circle
Capacitive reactance maps to lower half of unit circle
University of California, Berkeley EECS 117 Lecture 6 p. 22/
Complete Smith Chart
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Complete Smith Chart
u
r=0
r
=0
.5
r
=
1
x=
.5
x
=
1 x=2
x=-.5
x
=
-1
x=-2
v
short
open
match
r
=2
r > 1
inductive
capacitive
University of California, Berkeley EECS 117 Lecture 6 p. 23/
Load on Smith Chart
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Load on Smith Chart
load
First map zL on the Smith Chart as L
To read off the impedance on the T-line at any point ona lossless line, simply move on a circle of constant
radius since (z) = Le2j
University of California, Berkeley EECS 117 Lecture 6 p. 24/
Motion Towards Generator
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Motion Towards Generator
load
mov
emen
t towards generator
Moving towardsgenerator means
(
) = Le
2j, or
clockwise motionFor a lossy line, thiscorresponds to a
spiral motionWere back to wherewe started when
2 = 2, or = /2Thus the impedanceis periodic (as we
know)
University of California, Berkeley EECS 117 Lecture 6 p. 25/
SWR Circle
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SWR Circle
Since SWR is a function of ||, a circle at origin in(u,v) plane is called an SWR circle
SW
RC I R
C L E
voltage min voltage max
L = |L|ej
=
|L|ej(2)
Recall the voltage max
occurs when the reflectedwave is in phase with theforward wave, so(zmin) =
|L|This corresponds to the
intersection of the SWRcircle with the positive real
axis
Likewise, the intersectionwith the negative real axis
is the location of the voltgemin
University of California, Berkeley EECS 117 Lecture 6 p. 26/
Example of Smith Chart Visualization
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Example of Smith Chart Visualization
Prove that if ZL has an inductance reactance, then theposition of the first voltage maximum occurs before thevoltage minimum as we move towards the generator
A visual proof is easy using Smith Chart
On the Smith Chart start at any point in the upper halfof the unit circle. Moving towards the generator
corresponds to clockwise motion on a circle. Thereforewe will always cross the positive real axis first and thenthe negative real axis.
University of California, Berkeley EECS 117 Lecture 6 p. 27/
Impedance Matching Example
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Impedance Matching Example
Single stub impedance matching is easy to do with theSmith Chart
Simply find the intersection of the SWR circle with the
r = 1 circle
The match is at the center of the circle. Grab areactance in series or shunt to move you there!
University of California, Berkeley EECS 117 Lecture 6 p. 28/
Series Stub Match
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Series Stub Match
University of California, Berkeley EECS 117 Lecture 6 p. 29/
Admittance Chart
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Admittance Chart
Since y = 1/z = 11+ , you can imagine that an
Admittance Smith Chart looks very similar
In fact everything is switched around a bit and you canbuy or construct a combined admittance/impedancesmith chart. You can also use an impedance chart foradmittance if you simply map x
b and r
g
Be careful ... the caps are now on the top of the chartand the inductors on the bottom
The short and open likewise swap positions
University of California, Berkeley EECS 117 Lecture 6 p. 30/
Admittance on Smith Chart
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Admittance on Smith Chart
Sometimes you may need to work with bothimpedances and admittances.
This is easy on the Smith Chart due to the impedance
inversion property of a /4 line
Z =Z20
ZIf we normalize Z we get y
Z
Z0= Z0Z = 1z = y
University of California, Berkeley EECS 117 Lecture 6 p. 31/
Admittance Conversion
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Admittance Conversion
Thus if we simply rotate degrees on the Smith Chartand read off the impedance, were actually reading offthe admittance!
Rotating degrees is easy. Simply draw a line throughorigin and zL and read off the second point ofintersection on the SWR circle
University of California, Berkeley EECS 117 Lecture 6 p. 32/
Shunt Stub Match
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Shunt Stub Match
Lets now solve the same matching problem with ashunt stub.
To find the shunt stub value, simply convert the value of
z = 1 + jx to y = 1 + jb and place a reactance of jb inshunt
University of California, Berkeley EECS 117 Lecture 6 p. 33/