Adder
Transcript of Adder
Semi-Custom Design of Adiabatic Adder Circuits
V S Kanchana Bhaaskaran
S Salivahanan
SSN College of Engineering Chennai 603110
D.S.Emmanuel
Vellore Institute of Technology Vellore 632006
Abstract
The paper presents the design, evaluation andperformance comparison of cell based, low poweradiabatic adder circuits operated by two-phasesinusoidal power clock signals, as against theliteratures providing the operation of variousadiabatic circuits, focusing on inverter circuits andlogic gates, powered by ramp, three phase and fourphase clock signals. The cells are designed for thequasi-adiabatic families, namely, 2N2P, 2N2N2P, PFAL, ADSL and IPGL for configuring complex adder circuits. A family of adiabatic cell based designs forcarry lookahead adders and tree adders weredesigned. The simulations prove that the cell baseddesign of tree adder circuits can save energy rangingfrom 2 to 100 over a frequency range of operation of2MHz to 200MHz against the static CMOS circuitimplementation. The Schematic Edit and T-Spice ofTanner tools formed the simulation environment.
1. Introduction
The power consumption is the principal criterion for
the design and development of portable and high
performance applications. Hence, the trend has been to
search for techniques to reduce the power dissipation,
low power operation, and designing for energy
recovering and recycling. Energy recovery is proving a
promising approach for the design of low power VLSI
circuits. The primary advantage of adiabatic circuits
results from its inherent nature of deriving a constant
current from the power clock and the FETs working
with minimum voltage between the source and drain
terminals [1]. The adiabatic circuits are classified into
fully adiabatic and quasi-adiabatic circuit based on
whether full energy recovery or partial energy recovery
is obtained. The former has no non-adiabatic energy
loss, while the later suffers from both adiabatic and
non-adiabatic energy losses. The power supply
switching noise is generated by the effective
resistance(R) and inductance (Ldi/dt). When a number
of nodes in the circuit switch at the same time, the
effective switching current and hence, the rate of
change of current (di/dt) on the supply line can prove
very large. Since switching occurs with minimum
voltage drop across devices and both the signal and
power supply change slowly, very steep spikes are
effectively removed from the supply current, and this
results in appreciable reduction in switching noise.
The literatures have brought out several types and
genres of adiabatic circuits, namely, 2N-2P, 2N-
2N2P[2], PFAL [9], Pass Transistor Adiabatic Logic
(PAL) [3], Clocked Adiabatic Logic (CAL) [4],
Improved Pass-gate Adiabatic logic (IPGL) [5]
and Adiabatic Differential Switch Logic (ADSL) [6].
They are designed for special functions with custom
oriented designs. Design time is much longer and such
a full custom design is needed only in performance
critical applications. Standard cell-based designing is
therefore preferred for faster design of circuits.
Addition is one of the most commonly used
arithmetic operations. This work aims at cell-based
designing and comparison of 2N-2P, 2N-2N2P, PFAL,
IPGL and ADSL based adiabatic adder circuits.
Schematic designs are made for the individual AND,
XOR, NOT and MULTIPLEXER modules and they are
characterized. They are then employed in the full adder
cell design. This paper presents the design, evaluation,
performance analysis of 8-bit carry look ahead adders
and tree adders constructed using the adder cells
developed.
CIN
CO
A
S
B
Fig. 1 Schematic circuit of one bit full adder
Proceedings of the 19th International Conference on VLSI Design (VLSID’06) 1063-9667/06 $20.00 © 2006 IEEE
VPC
OUTBAR
FBARF
OUT
VPC
OUT
FFB
OUTB
OUT
VPC
F FBAR
OUTB
(a) (b) (c)VPC
FBAR F
OUTBAR
FBARF
OUT
VPCB
VPC
F
VPCB
VPC
OUT OUTB
VPC
FBAR
(d) (e)
Fig.2 Adiabatic circuit families (a) 2N2P
(b) 2N2N2P (c) PFAL (d) IPGL (e) ADSL
2. Adiabatic Cell Design and Design Flow
The realization of full adder is done in a semi-
automatic custom flow as depicted in Fig.1. Fig. 2
depicts the typical circuit arrangement of the adiabatic
circuit families. The individual modules are
constructed using the S-Edit and the designs are
exported to the T-Spice circuit Simulator. The
operational feasibility of the gate is studied for various
frequency ranges and capacitive loads. The functional
block diagram of the full adder circuit is shown in
Fig.3.
3. Adiabatic Adder Designs
The ripple carry adder design was not preferred due
to its reduced speed of operation. Hence the carry
lookahead adder (CLA) structure [7] that possesses
faster carry computation ability and a tree-structured
adder [8] were selected for our study. A cell generator
in C++ program was developed to synthesize the
architecture for structure of the CLA circuit. Fig.4
shows the general schematic arrangement of the
adiabatic 8-bit CLA architecture.
Fig.5 shows the schematic view of a tree adder. The
adder highlighted with a star identifies the full adder
driven by and driving a similar full adder with the
respective sum and carry outputs. We designed a
combinational CMOS one bit adder for comparison.
BBAR
CINBAR
VPC2
XOR
VPC1
A
CIN
SBAR
B
NAND
S
BUFABAR XOR
CO
NAND NAND
COBAR
BUF
Fig.3 Adiabatic Full Adder Block Configuration
S1
CO
B1
B4
S7
A4
S0
S5
S2
A0
B7
B2
A7
S4
A3
B6
B5
A5
B0
A2
S6
A1
B3
A6
S3
Fig. 4. Schematic view of the 8-bit CLA architecture
The literatures provide different one-bit adder
topologies. For a logical evaluation, the same structural
arrangement as followed for adiabatic adders, viz., by
the use of XOR, AND and BUF gate modules was
followed for CMOS adder also.
4. Performance Evaluation and
Comparison
The results of the simulation are presented in this
section. Each of the full adders was analyzed for
energy consumption and the number of transistor
devices employed in the design, which is an indication
of the actual silicon area requirement for the circuit.
The inputs A, B and Ci were supplied as per the
three bit binary counting sequence for uniformity. The
frequency of the power clock was varied from 100Hz
to 200MHz.
The energy dissipation measurement was done from
the simulation outputs, by integrating the power over
the specific period of simulation, which varied from
320ns to 640ms. The average power dissipation of the
circuit was also observed. Fig.6 shows the energy
comparisons made among the adiabatic families
with
S5
B
S5
2 0
1 8
A4
B4
C 4
A4
B
B4
B
C 4
B
A3
B3
C 3
A3
B
B3
B
C 3
B
A2
B2
C 2
A2
B
B2
B
C 2
B
A1
B1
C 1
A1
B
B1
B
C 1
B
A0
B0
C 0
A0
B
B0
B
C 0
B
S0S0
B
S4S4
B
VPC
1
VPC
2
VPC
1
VPC
2
VPC
1
VPC
2
VPC
1
VPC
2
VPC
1
VPC
2
VPC
1
VPC
2
VPC
1
VPC
2
VPC
1
VPC
2
VPC
1
VPC
2
VPC
1
VPC
2
VPC
1
VPC
2
VPC
2
VPC
1
C BSB C S
12
345678
91 0
1 11 2
1 31 41 5
1 6
2 1
F A
PF
AL
F A
PF
AL
F A
PF
AL
FA
PF
AL
FA
PF
AL
F A
PF
AL
F A
PF
AL
F A
PF
AL
F A
PF
AL
F A
PF
AL
FA
PF
AL
F A
PF
AL
Fig.5 Schematic View of Tree Adder Structure
Proceedings of the 19th International Conference on VLSI Design (VLSID’06) 1063-9667/06 $20.00 © 2006 IEEE
-0.10
-0.05
0.00
200100101
Frequency, MHz
En
erg
y, p
J2N2P 2N2N2P IPGL ADSL CMOS
Fig. 6. Energy comparison of adiabatic adders with
no load capacitances.
-6.E-08
-4.E-08
-2.E-08
0.E+00
0 10 20 30 40 50 60 70 80
Load Capacitance, fF
En
erg
y, J
IPGL 2N2N2P
2N2P CMOS
Fig.7. Energy comparison of 2N2NP, 2N2N2P
AND IPGL adiabatic adders
no load at the sum and carry terminals. The negative
sign indicates the energy dissipated in the circuit. Fig.7
gives the energy consumption for different capacitive
loads for 2N2P, 2N2N2P and IPGL adiabatic adders.
These adders were found to possess higher load-
driving capability than the PFAL and ADSL families,
whose performance is shown in Fig.8. It is to be
pointed out that the PFAL was reported in [9] as
demonstrating the lowest power consumption. Our
work shows that the PFAL adiabatic when driven by
two-phase sinusoidal power clock is more energy
consuming as depicted in Fig. 8 even for low capacity
load conditions.
Figs.9 and 10 show the energy comparisons made
for the 8-bit carry lookahead adder and tree adder
circuits of various adiabatic families The energy
consumption comparisons [9] were made, and the
concept of adiabatic gain G (the ratio between the
energy dissipated by the CMOS gate and the
equivalent adiabatic gate) is used. The Table 1 shows
the transistor counts of the CLA and tree based adder
circuits. The adiabatic gain, G for the case of tree
adder is tabulated in the Table 2 for
comparison.
Table.1 Transistor counts for CLA and Tree Adders
PFAL 2N2P 2N2N2P ADSL
8-BIT CLA 936 700 936 1440
TREE ADDER 648 504 648 936
-8.E-07
-6.E-07
-4.E-07
-2.E-07
0.E+00
0FF 2 4 8 10 14 16
Load Capacitance, fF
En
erg
y,J
PFAL
ADSL
Fig.8. Energy comparison of PFAL and ADSL
adiabatic adders
-3E-07-2E-07-1E-070
300MEG
200MEG
100MEG
Fre
qu
nc
y, M
Hz
Energy, J
2N2N2P 2N2P PFAL ADSL
Fig. 9. Energy comparisons made for 8-bit CLA for
the 2N2P, 2N2N2P, PFAL and ADSL
It can be noted that the adiabatic gain varies from
101.2 at 2MHz to 2.3 at 200MHz as against the
CMOS tree adder.
5. Power Clock Generation
The power clocks used in adiabatic circuits provide
the power for the circuit and behave as clock also.
The resonant energy recovery topology based
on synchronous clock generation is used for clock
generation with the internal time base signals used as
clock timing signals. Current charging as necessitated
for adiabatic circuits is approximated using the
sinusoidal power supply generated by the LC resonant
-1
-0.9
-0.8
-0.7
-0.6
-0.5
-0.4
-0.3
-0.2
-0.10
200MEG
100MEG
50MEG
20MEG
2MEG
Fre
qu
en
cy
, M
Hz
Energy, pJ
2N2P
2N2N2P
CMOS
PFAL
ADSL
Fig. 10. Energy comparisons made for the tree adders
Proceedings of the 19th International Conference on VLSI Design (VLSID’06) 1063-9667/06 $20.00 © 2006 IEEE
Table.2 Energy consumption and adiabatic gain of
the tree adders with respect to CMOS adders
2N2P2N2N2P
PFAL IPGL
2N CLK
-1.5E-10
-1E-10
-5E-11
0Adiabatic family
En
erg
y, J
Fig. 11. Power dissipation incurred in the adiabatic
inverters and the clock generator circuit
single phase power clock generator circuit of Fig 12.
The circuit modeling was done initially. For a power
loss of , R=LP 2LL IP and C= cDDL fVI2 for a
particular frequency of the clock. The power
conversion efficiency of the clock generator is defined
as the ratio of the total dissipated load power to the total
supply power delivered by the DC supply. It can be
observed that the energy consumed by the clock
generator for its power clock generation is
comparatively less than that consumed by the inverters
of various logic families as shown in Fig. 13.
cf
6. Conclusion
This paper proves the feasibility of operating
the adiabatic circuits by two-phase sinusoidal clock
signals, and, the feasibility of semi custom modular
design approaches for adiabatic designs. The work
compares the adiabatic full adder circuits and multi bit
adder circuits.
For high frequency of operations, the IPGL could
be employed though at higher transistor count and more
area. The 2N-2P and 2N-2N2P circuits provide good
performance at higher frequencies. The Full adder
performance shows that the PFAL circuit experiences
high-energy consumption in high frequency
applications, and ADSL, 2N2P, 2N2N2P and IPGL are
proved to be preferable. The results of Fig. 8 and 9
show that the 2N2P, 2N2N2P and IPGL are more
suitable for operating under high load capacitance
situations as against the ADSL and PFAL based
circuits. It is also observed that the ADSL based adder
is preferable for low voltage and low frequency high
performance applications. The transients in the CMOS
circuits are orders of magnitude higher in comparison
with the adiabatic circuits. The sinusoidal frequency
generates less noise and the skew does not dominate.
Energy savings are achieved in the circuit, even taking
into account the energy consumed for the clock
generation circuitry. The results also show that the
adiabatic circuits could be the most suitable choice,
when the power consumption is considered the primary
criteria for the given range of frequencies.
2N2N2P 2N2P ADSL ADSLM PFAL
200MEG -0.255 -0.229 -0.889 -0.928 -0.604
2.081 2.320 0.598 0.573 0.879100MEG -0.241 -0.127 -0.555 -0.619 -0.529
2.208 4.183 0.958 0.859 1.00550MEG -0.162 -0.093 -0.469 -0.433 -0.302
3.283 5.711 1.132 1.229 1.76120MEG -0.067 -0.048 -0.384 -0.310 -0.122
7.942 10.973 1.383 1.712 4.3722MEG -0.007 -0.005 -0.251 -0.036 -0.010
72.432 101.218 2.113 14.908 50.873
7. Reference
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Proceedings of the 19th International Conference on VLSI Design (VLSID’06) 1063-9667/06 $20.00 © 2006 IEEE