Wireless Power AoP

8/4/2019 Wireless Power AoP

1/15

Efficient wireless non-radiative mid-rangeenergy transfer

Aristeidis Karalis a,*, J.D. Joannopoulos b, Marin Soljacic b

a Department of Electrical Engineering and Computer Science, Massachusetts Institute of Technology,

77 Massachusetts Avenue, Cambridge, MA 02139, USAb Department of Physics, Massachusetts Institute of Technology, 77 Massachusetts Avenue,

Cambridge, MA 02139, USA

Received 17 April 2007; accepted 17 April 2007Available online 27 April 2007

Abstract

We investigate whether, and to what extent, the physical phenomenon of long-lifetime resonantelectromagnetic states with localized slowly-evanescent field patterns can be used to transfer energyefficiently over non-negligible distances, even in the presence of extraneous environmental objects.Via detailed theoretical and numerical analyses of typical real-world model-situations and realisticmaterial parameters, we establish that such a non-radiative scheme can lead to strong couplingbetween two medium-range distant such states and thus could indeed be practical for efficient med-ium-range wireless energy transfer. 2007 Elsevier Inc. All rights reserved.

Keywords: Wireless energy; Wireless power; Strong coupling

1. Introduction

In the early days of electromagnetism, before the electrical-wire grid was deployed, seri-ous interest and effort was devoted (most notably by Nikola Tesla [1]) towards the devel-opment of schemes to transport energy over long distances without any carrier medium(e.g. wirelessly). These efforts appear to have met with little success. Radiative modes of

0003-4916/$ - see front matter 2007 Elsevier Inc. All rights reserved.

doi:10.1016/j.aop.2007.04.017

*

Corresponding author. Fax: +1 617 253 2562.E-mail address: [email protected] (A. Karalis).

Available online at www.sciencedirect.com

Annals of Physics 323 (2008) 3448

www.elsevier.com/locate/aop
mailto:[email protected]:[email protected]


2/15

omni-directional antennas (which work very well for information transfer) are not suitablefor such energy transfer, because a vast majority of energy is wasted into free space.Directed radiation modes, using lasers or highly-directional antennas, can be efficientlyused for energy transfer, even for long distances (transfer distance LTRANS LDEV, where

LDEV is the characteristic size of the device), but require existence of an uninterruptibleline-of-sight and a complicated tracking system in the case of mobile objects. Rapiddevelopment of autonomous electronics of recent years (e.g. laptops, cell-phones,house-hold robots, that all typically rely on chemical energy storage) justifies revisitinginvestigation of this issue. Today, we face a different challenge than Tesla: since the exist-ing electrical-wire grid carries energy almost everywhere, even a medium-range(LTRANS % few*LDEV) wireless energy transfer would be quite useful for many applica-tions. There are several currently used schemes, which rely on non-radiative modes(magnetic induction), but they are restricted to very close-range (LTRANS LDEV) or verylow-power (

$mW) energy transfers [26].

In contrast to all the above schemes, we investigate the feasibility of using long-livedoscillatory resonant electromagnetic modes, with localized slowly-evanescent field patterns,for efficient wireless non-radiative mid-range energy transfer. The proposed method is basedon the well known principle of resonant coupling (the fact that two same-frequency reso-nant objects tend to couple, while interacting weakly with other off-resonant environmentalobjects) and, in particular, resonant evanescent coupling (where the coupling mechanism ismediated through the overlap of the non-radiative near-fields of the two objects). This wellknown physics leads trivially to the result that energy can be efficiently coupled betweenobjects in the extremely near field (e.g. in optical waveguide or cavity couplers and in res-

onant inductive electric transformers). However, it is far from obvious how this same phys-ics performs at mid-range distances and, to our knowledge, there is no work in the literaturethat demonstrates efficient energy transfer for distances a few times larger that the largestdimension of both objects involved in the transfer. In the present paper, our detailed the-oretical and numerical analysis shows that such an efficient mid-range wireless energy-exchange can actually be achieved, while suffering only modest transfer and dissipationof energy into other off-resonant objects, provided the exchange system is carefullydesigned to operate in a regime of strong coupling compared to all intrinsic loss rates.The physics of strong coupling is also known but in very different areas, such as thoseof light-matter interactions [7]. In this favorable operating regime, we quantitatively

address the following questions: up to which distances can such a scheme be efficient andhow sensitive is it to external perturbations? The omnidirectional but stationary (non-lossy)nature of the near field makes this mechanism suitable for mobile wireless receivers. It couldtherefore have a variety of possible applications including for example, placing a source(connected to the wired electricity network) on the ceiling of a factory room, while devices(robots, vehicles, computers, or similar) are roaming freely within the room. Other possibleapplications include electric-engine buses, RFIDs, and perhaps even nano-robots.

2. Range and rate of coupling

The range and rate of the proposed wireless energy-transfer scheme are the first subjectsof examination, without considering yet energy drainage from the system for use intowork. An appropriate analytical framework for modeling this resonant energy-exchangeis that of the well-known coupled-mode theory (CMT) [8]. In this picture, the field of

A. Karalis et al. / Annals of Physics 323 (2008) 3448 35


3/15

the system of two resonant objects 1 and 2 is approximated by F(r, t) % a1(t)F1(r) +a2(t)F2(r), where F1,2(r) are the eigenmodes of 1 and 2 alone, and then the field amplitudesa1(t) and a2(t) can be shown [8] to satisfy, to lowest order:

da1

dt ix1 iC1a1 ija2da2dt

ix2 iC2a2 ija1; 1

where x1,2 are the individual eigenfrequencies, C1,2 are the resonance widths due to theobjects intrinsic (absorption, radiation, etc.) losses, and j is the coupling coefficient.Eqs. (1) show that at exact resonance (x1 = x2 and C1 = C2), the normal modes of thecombined system are split by 2j; the energy exchange between the two objects takes placein time $p/2kand is nearly perfect, apart for losses, which are minimal when the couplingrate is much faster than all loss rates (j ) C1,2).1 It is exactly this ratio j=

ffiffiffiffiffiffiffiffiffiffiC1C2

pthat we

will set as our figure-of-merit for any system under consideration for wireless energy-trans-

fer, along with the distance over which this ratio can be achieved. The desired optimal re-gime j=ffiffiffiffiffiffiffiffiffiffiC1C2

p ) 1 is called strong-coupling regime.Consequently, our energy-transfer application requires resonant modes of high Q = x/

2C for low (slow) intrinsic-loss rates C, and this is why we propose a scheme where thecoupling is implemented using, not the lossy radiative far-field, but the evanescent (non-lossy) stationary near-field. Furthermore, strong (fast) coupling rate j is required over dis-tances larger than the characteristic sizes of the objects, and therefore, since the extent ofthe near-field into the air surrounding a finite-sized resonant object is set typically by thewavelength (and quantified rigorously by the radiation caustic), this mid-range non-radiative coupling can only be achieved using resonant objects of subwavelength size,

and thus significantly longer evanescent field-tails. This is a regime of operation thathas not been studied extensively, since one usually prefers short tails to minimize interfer-ence with nearby devices. As will be seen in examples later on, such subwavelength reso-nances can often be accompanied with a high radiation-Q, so this will typically be theappropriate choice for the possibly-mobile resonant device-object d. Note, though, thatthe resonant source-object s will in practice often be immobile and with less stringentrestrictions on its allowed geometry and size, which can be therefore chosen large enoughthat the near-field extent is not limited by the wavelength (using for example waveguideswith guided modes tuned close to the light line in air for slow exponential decaytherein).

The proposed scheme is very general and any type of resonant structure (e.g.electromagnetic, acoustic, nuclear) satisfying the above requirements can be used for itsimplementation. As examples and for definiteness, we choose to work with twowell-known, but quite different, electromagnetic resonant systems: dielectric disks andcapacitively-loaded conducting-wire loops. Even without optimization, and despite theirsimplicity, both will be shown to exhibit acceptably good performance.

1

The CMT model is valid exactly for this optimal operational regime of well-defined resonances. Its range ofapplicability does not include very-close-distance coupling, since there the necessary condition j x1,2 does nothold, neither large-distance far-field coupling, since it fails to predict far-field interference effects and accurateradiation patterns; rather CMT is exactly suitable for the medium-distance near-field coupling of our interest.Thus the use of this model is justified and the parameters j, C1,2 are well defined.

36 A. Karalis et al. / Annals of Physics 323 (2008) 3448


4/15

2.1. Dielectric disks

Consider a 2D dielectric disk object of radius r and relative permittivity e surrounded byair that supports high-Q whispering-gallery resonant modes (Fig. 1). The loss mecha-

nisms for the energy stored inside such a resonant system are radiation into free spaceand absorption inside the disk material. High-Qrad and long-tailed subwavelength reso-nances can be achieved, only when the dielectric permittivity e is large and the azimuthalfield variations are slow (namely of small principal number m). Material absorption isrelated to the material loss tangent: Qabs $ Re{e}/Im{e}. Mode-solving calculations forthis type of disk resonances were performed using two independent methods: numerically,2D finite-difference frequency-domain (FDFD) simulations (which solve Maxwells Equa-tions in frequency domain exactly apart for spatial discretization) were conducted with a

Fig. 1. Main plot. A 2D high-e disk of radius r (shown in yellow) surrounded by air, along with the electric field(with polarization pointing out of the page) of its resonant whispering-gallery mode superimposed (shown in red/white/blue in regions of positive/zero/negative field respectively). Side plot. Radial plot of the electric field of themode shown in the main plot (basically a cross-section of the main plot). Note that in air (radius/r > 1) the fieldfollows a Hankel-function form, with an initial exponential-like regime (with long tails compared to the small disksize), followed by the oscillatory/radiation regime (whose presence means that energy is slowly leaking out of thedisk). Table. Numerical FDFD (and in parentheses analytical SV) results for the wavelength and absorption,radiation and total loss rates, for two different cases of subwavelength-disk resonant modes. Note that disk-

material loss-tangent Im{e}/Re{e}=104

was used. (The specific parameters of the plot are highlighted with bold inthe table.) Finally, note that for the 3D case the computational complexity would be immensely increased, whilethe physics would not be significantly different. For example, a spherical object of e = 147.7 has a whisperinggallery mode with m = 2, Qrad = 13,962, and k/r = 17. (For interpretation of the references to color in this figurelegend, the reader is referred to the web version of this paper.)



5/15

resolution of 30 pts/r; analytically, standard separation of variables (SV) in polar coordi-nates was used. The results for two TE-polarized dielectric-disk subwavelength modes ofk/rP 10 are presented in Fig. 1. The two methods have excellent agreement and implythat for a properly designed resonant low-loss-dielectric object values of QradP 2000

and Qabs $ 10,000 should be achievable.Note that the required values of e, shown in Fig. 1, might at first seem unrealistically

large. However, not only are there in the microwave regime (appropriate for meter-rangecoupling applications) many materials that have both reasonably high enough dielectricconstants and low losses (e.g. Titania: e % 96, Im{e}/e % 103; Barium tetratitanate:e % 37, Im{e}/e % 104; Lithium tantalite: e % 40, Im{e}/e % 104; etc.) [9,10], but also ecould signify instead the effective index of other known subwavelength (k/r ) 1) sur-face-wave systems, such as surface-plasmon modes on surfaces of metal-like (negative-e)materials [11] or metallo-dielectric photonic crystals [12].

To calculate now the achievable rate of energy transfer between two disks 1 and 2, weplace them at distance D between their centers (Fig. 2). Numerically, the FDFD mode-sol-ver simulations give j through the frequency splitting (=2j) of the normal modes of thecombined system, which are even and odd superpositions of the initial single-disk modes;analytically, using the expressions for the separation-of-variables eigenfields E1,2(r) CMTgives j through j x1=2

Rd3re2rE2rE1r=

Rd3rerjE1rj2, where ej(r) and e(r) are

the dielectric functions that describe only the disk j (minus the constant eo background)and the whole space respectively. Then, for medium distances D/r = 103 and for non-radiative coupling such that D < 2rC, where rC = mk/2p is the radius of the radiation caus-tic, the two methods agree very well, and we finally find (Fig. 2) coupling-to-loss ratios in

the range j/C $ 150. Although the achieved figure-of-merit values do not fall in the idealstrong-coupling operating regime j/C ) 1, they are still large enough to be useful forapplications, as we will see later on.

2.2. Capacitively-loaded conducting-wire loops

Consider a loop of radius r of conducting wire with circular cross-section of radius aconnected to a pair of conducting parallel plates of area A spaced by distance d via adielectric of relative permittivity e and everything surrounded by air (Fig. 3). The wirehas inductance L, the plates have capacitance Cand then the system has a resonant mode,

where the nature of the resonance lies in the periodic exchange of energy from the electricfield inside the capacitor, due to the voltage across it, to the magnetic field in free space,due to the current in the wire. Losses in this resonant system consist of ohmic loss Rabsinside the wire and radiative loss Rrad into free space. Mode-solving calculations for thistype of RLC-circuit resonances were performed using again two independent methods:numerically, 3D finite-element frequency-domain (FEFD) simulations (which solve Max-wells Equations in frequency domain exactly apart for spatial discretization) were con-ducted [13], in which the boundaries of the conductor were modeled using a compleximpedance gc

ffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffilcx=2r

pboundary condition, valid as long as gc/go ( 1 [14] (


6/15

the resonant frequency x 1= ffiffiffiffiffiffiffiLCp and its quality factors Qabs = xL/Rabs and Qrad = xL/Rrad. By tuning the capacitance and thus the resonant frequency, the total Q becomeshighest for some optimal frequency determined by the loop parameters: at low frequenciesit is dominated by ohmic loss and at high frequencies by radiation. The results for two sub-wavelength modes ofk/rP 70 (namely highly suitable for near-field coupling and really inthe quasi-static limit) at this optimal frequency are presented in Fig. 3. The two methodsare again in very good agreement and show that expected quality factors in the microwave

are QabsP 1000 and Q

radP 10,000.

For the rate of energy transfer between two loops 1 and 2 at distance D between theircenters (Fig. 4): numerically, the FEFD mode-solver simulations give j again through thefrequency splitting (=2j) of the normal modes of the combined system; analytically, j is

Fig. 2. Plot. System of two same 2D high-e disks of radius r (yellow) for medium-distance D coupling betweenthem, along with the electric field of the normal mode, which is an even superposition of the single-disk modes ofFig. 1, superimposed (red/white/blue). Note that there is also a normal mode, which is an odd superposition ofthe single-disk modes ofFig. 1 (not shown). Table. Numerical FDFD (and in parentheses analytical CMT) resultsfor the average of the wavelength and loss rates of the two normal modes (individual values not shown), and alsothe coupling rate and strong/weak-coupling figure-of-merit as a function of the coupling distance D, for thetwo cases of disk modes presented in Fig. 1. Only distances for non-radiative (D < 2rC) coupling are considered.Note that the average Crad (and thus total C) shown are slightly different from the single-disk value of Fig. 1, dueto far-field interference effects present for the two normal modes, for which CMT cannot make predictions andthis is why analytical results for Crad are not shown but the single-disk value is used. (The specific parameters ofthe plot are highlighted with bold in the table.) (For interpretation of the references to color in this figure legend,the reader is referred to the web version of this paper.)



7/15

given by j xM=2 ffiffiffiffiffiffiffiffiffiL1L2p , where M is the mutual inductance of the two loops, which, inthe quasi-static limit r D k and for the relative orientation shown in Fig. 4, is M% p/2lo(r1r2)

2/D3 [14], which means that x=2j $ D= ffiffiffiffiffiffiffiffir1r2p 3. Then, and for medium distancesD/r = 103, the two methods agree well, and we finally find (Fig. 4) coupling-to-lossratios, which peak at a frequency between those where the single-loop Q1,2 peak and

are in the range j/C $ 0.550.It is important to appreciate the difference between such a resonant-coupling inductive

scheme and the well-known non-resonant inductive scheme for energy transfer. UsingCMT it is easy to show that, keeping the geometry and the energy stored at the sourcefixed, the resonant inductive mechanism allows for $Q2 ($106) times more power deliv-ered for work at the device than the traditional non-resonant mechanism. This is why onlyclose-range contact-less medium-power ($W) transfer is possible with the latter [2,3],while with resonance either close-range but large-power ($kW) transfer is allowed [4,5]or, as currently proposed, if one also ensures operation in the strongly-coupled regime,medium-range and medium-power transfer is possible. Capacitively-loaded conductive

loops are actually being widely used also as resonant antennas (for example in cellphones), but those operate in the far-field regime with D/r 1,r/k $ 1, and the radiationQs are intentionally designed to be small to make the antenna efficient, so they are notappropriate for energy transfer.

Fig. 3. Plot. A wire loop of radius r connected to a pair ofd-spaced parallel plates (shown in yellow) surroundedby air, along with a slice of the magnetic field (component parallel to the axis of the circular loop) of theirresonant mode superimposed (shown in red/white/blue in regions of positive/zero/negative field respectively).Table. Numerical FEFD (and in parentheses analytical) results for the wavelength and absorption, radiation and

total loss rates, for two different cases of subwavelength-loop resonant modes. Note that for conducting materialcopper (r = 5.998 107 S/m) was used. (The specific parameters of the plot are highlighted with bold in the table.)(For interpretation of the references to color in this figure legend, the reader is referred to the web version of thispaper.)



8/15

3. Influence of extraneous objects

Clearly, the success of the proposed resonance-based wireless energy-transfer schemedepends strongly on the robustness of the objects resonances. Therefore, their sensitivityto the near presence of random non-resonant extraneous objects is another aspect of theproposed scheme that requires analysis. The appropriate analytical model now is that ofperturbation theory (PT) [8], which suggests that in the presence of an extraneous object

e the field amplitude a1(t) inside the resonant object 1 satisfies, to first order:

da1dt

i x1 iC1 a1 i j11e iC1e a1 2

Fig. 4. Plot. System of two same wire loops connected to parallel plates (yellow) for medium-distance D couplingbetween them, along with a slice of the magnetic field of the even normal mode superimposed (red/white/blue).Note that there is also an odd normal mode (not shown). Table. Numerical FEFD (and in parentheses analytical)results for the average wavelength and loss rates of the two normal modes (individual values not shown), and alsothe coupling rate and strong/weak-coupling figure-of-merit as a function of the coupling distance D, for thetwo cases of modes presented in Fig. 3. Note that the average Crad shown are again slightly different from thesingle-loop value ofFig. 3, due to far-field interference effects present for the two normal modes, which again theanalytical model cannot predict and thus analytical results for Crad are not shown but the single-loop value is

used. (The specific parameters of the plot are highlighted with bold in the table.) (For interpretation of thereferences to color in this figure legend, the reader is referred to the web version of this paper.)



9/15

where again x1 is the frequency and C1 the intrinsic (absorption, radiation, etc.) loss rate,while j11e is the frequency shift induced onto 1 due to the presence of e and C1e is theextrinsic due to e (absorption inside e, scattering from e, etc.) loss rate2. The frequencyshift is a problem that can be fixed rather easily by applying to every device a feedback

mechanism that corrects its frequency (e.g. through small changes in geometry) andmatches it to that of the source. However, the extrinsic loss can be detrimental to the func-tionality of the energy-transfer scheme, because it cannot be remedied, so the total lossrate C1[e] = C1 + C1e and the corresponding figure-of-merit je=

ffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiC1eC2e

p, where j[e]

the perturbed coupling rate, must be quantified.

3.1. Dielectric disks

In the first example of resonant objects that we have considered, namely dielectric disks,small, low-index, low-material-loss or far-away stray objects will induce small scatteringand absorption. In such cases of small perturbations these extrinsic loss mechanismscan be quantified using respectively the analytical first-order PT formulasCrad1e / x1

Rd3rjRefeergj2jE1rj2=U and Cabs1e x1=4

Rd3rImfeergjE1rj2=U, where

U 1=2 Rd3rerjE1rj2 is the total resonant electromagnetic energy of the unperturbedmode. As one can see, both of these losses depend on the square of the resonant electricfield tails E1 at the site of the extraneous object. In contrast, the coupling rate from object1 to another resonant object 2 is, as stated earlier, j x1=4

Rd3re2rE2rE1r=U and

depends linearly on the field tails E1 of 1 inside 2. This difference in scaling gives us con-fidence that, for exponentially small field tails, coupling to other resonant objects should

be much faster than all extrinsic loss rates (j ) C1e), at least for small perturbations, andthus the energy-transfer scheme is expected to be sturdy for this class of resonant dielectricdisks.

However, we also want to examine certain possible situations where extraneous objectscause perturbations too strong to analyze using the above first-order PT approach. Forexample, we place a dielectric disk c close to another off-resonance object of largeRe{e}, Im{e} and of same size but different shape (such as a human being h), as shownin Fig. 5a, and a roughened surface of large extent but of small Re{e}, Im{e} (such as awall w), as shown in Fig. 5b. For distances Dh/w/r = 103 between the disk-center andthe human-center/wall, the numerical FDFD simulation results presented in Fig. 5

suggest that Qradch;Q

radcw P 1000 (instead of the initial Q

radc P 2000, Q

absc $ 10; 000 (natu-

rally unchanged), Qabsch $ 105102, and Qabscw $ 105104, namely the disk resonance seemsto be fairly robust, since it is not detrimentally disturbed by the presence of extraneousobjects, with the exception of the very close proximity of high-loss objects [16].

To examine the influence of large perturbations on an entire energy-transfer system weconsider two resonant disks in the close presence of both a human and a wall. Thenumerical FDFD simulations show that the system performance deteriorates from j/Cc $ 150 (Fig. 2) to j[hw]/Cc[hw] $ 0.510 (Fig. 6), i.e. only by acceptably small amounts.

2 The first-order PT model is valid only for small perturbations. Nevertheless, the parameters j11e, C1e arewell defined, even outside that regime, if a1 is taken to be the amplitude of the exact perturbed mode.



10/15

3.2. Capacitively-loaded conducting-wire loops

In the second example of resonant objects that we have considered, the conducting-wireloops, the influence of extraneous objects on the resonances is nearly absent. The reason isthat, in the quasi-static regime of operation (r k) that we are considering, the near field inthe air region surrounding the loop is predominantly magnetic (since the electric field islocalized inside the capacitor), therefore extraneous non-metallic objects e that could inter-act with this field and act as a perturbation to the resonance are those having significant

magnetic properties (magnetic permeability Re{l} > 1 or magnetic loss Im{l} > 0). Sincealmost all every-day materials are non-magnetic, they respond to magnetic fields in thesame way as free space, and thus will not disturb the resonance of a conducting-wire loop.To get only a rough estimate of this disturbance, we use the PT formula, stated earlier,

Fig. 5. Plots. A disk (yellow) in the proximity at distance Dh/w of an extraneous object (yellow): (a) a high

e = 49 + 16i (which is large but actually appropriate for human muscles in the GHz regime [16]) square object ofsame size (area) with the disk, and (b) a large roughened surface of e = 2.5 + 0.05i (appropriate for ordinarymaterials such as concrete, glass, plastic, wood [16]), along with the electric field of the disks perturbed resonantmode superimposed (red/white/blue). Tables. Numerical FDFD results for the parameters of the disks perturbedresonance, including absorption rate inside the extraneous object and total (including scattering from theextraneous object) radiation-loss rate, for the two cases of disk modes presented in previous figures. Note thatagain disk-material loss-tangent Im{e}/Re{e}=104 was used, and that Qradch=w is again different (decreased or evenincreased) from the single-disk Qradc ofFig. 1, due to (respectively constructive or destructive) interference effectsthis time between the radiated and strongly scattered far-fields. (The specific parameters of the plots are highlightedwith bold in the tables.) (For interpretation of the references to color in this figure legend, the reader is referred tothe web version of this paper.)



11/15

Cabs1e x1=4 R

d3r ImfeergjE1rj2=Uwith the numerical results for the field of an exam-ple like the one shown in the plot of Fig. 4 and with a rectangular object of dimensions30 cm 30 cm 1.5 m and permittivity e = 49 + 16i (human muscles) residing betweenthe loops and almost standing on top of one capacitor ($3 cm away from it) and findQabsc

h

$105 and for

$10 cm away Qabsc

h

$5

105. Thus, for ordinary distances (

$1 m)

and placements (not immediately on top of the capacitor) or for most ordinary extraneousobjects e of much smaller loss-tangent, we conclude that it is indeed fair to say thatQabsce ! 1 and that j[e]/C[e] $ j/C $ 0.550. The only perturbation that is expected toaffect these resonances is a close proximity of large metallic structures.

Fig. 6. Plot. System of two same disks (yellow) for medium-distance D coupling between them in the proximity atequal distance D of two extraneous objects (yellow): both a high e = 49 + 16i square object of same size (area)with the disks and a large roughened surface of e = 2.5 + 0.05i, along with the electric field of the systemsperturbed even normal mode superimposed (red/white/blue). Table. Numerical FDFD results for the averagewavelength and loss rates of the systems perturbed two normal modes (individual values not shown), and also theperturbed coupling rate and strong/weak-coupling figure-of-merit as a function of the distance D, for the twocases of disk modes presented in previous Figures. Only distances for non-radiative ( D < 2rC) coupling are

considered. Note once more that the average Crad

takes into account interference effects between all radiated andscattered far-fields. (The specific parameters of the plot are highlighted with bold in the table.) (For interpretation ofthe references to color in this figure legend, the reader is referred to the web version of this paper.)



12/15

An extremely important implication of this fact relates to safety considerations forhuman beings. Humans are also non-magnetic and can sustain strong magnetic fields with-out undergoing any risk. A typical example, where magnetic fields B$ 1 T are safely usedon humans, is the magnetic resonance imaging (MRI) technique for medical testing. In

contrast, the magnetic near-field required by our scheme in order to provide a few Wattsof power to devices is only B$ 104 T, which is actually comparable to the magnitude ofthe Earths magnetic field. Since, as explained above, a strong electric near-field is also notpresent and the radiation produced from this non-radiative scheme is minimal, it is reason-able to expect that our proposed energy-transfer method should be safe for livingorganisms.

In comparison of the two classes of resonant systems under examination, the strongimmunity to extraneous objects and the absence of risks for humans probably makesthe conducting-wire loops the preferred choice for many real-world applications; on theother hand, systems of disks (or spheres) of high (effective) refractive index have theadvantage that they are also applicable to much smaller length-scales (for example inthe optical regime dielectrics prevail, since conductive materials are highly lossy).

4. Efficiency of energy-transfer scheme

Consider again the combined system of a resonant source s and device din the presenceof a set of extraneous objects e, and let us now study the efficiency of this resonance-basedenergy-transfer scheme, when energy is being drained from the device at rate Cwork for useinto operational work. The coupled-mode-theory equation for the device field-amplitude is

daddt

ix iCdead ijeas Cworkad; 3

where Cde Cradde Cabsde Cradde Cabsd Cabsde is the net perturbed-device loss rate, andsimilarly we define Cs[e] for the perturbed-source. Different temporal schemes can be usedto extract power from the device (e.g. steady-state continuous-wave drainage, instanta-neous drainage at periodic times and so on) and their efficiencies exhibit different depen-dence on the combined system parameters. Here, we assume steady state, such that thefield amplitude inside the source is maintained constant, namely as(t) = Ase

ixt, so then

the field amplitude inside the device is ad(t) = Adeixt

with Ad=As ije=Cde Cwork.The various time-averaged powers of interest are then: the useful extracted power isPwork = 2CworkjAdj2, the radiated (including scattered) power is Prad 2Cradse jAsj22CraddejAdj2, the power absorbed at the source/device is Ps=d 2Cabss=djAs=dj2, and at the extra-neous objects Pe 2CabssejAsj2 2CabsdejAdj2. From energy conservation, the total time-aver-aged power entering the system is Ptotal = Pwork + Prad + Ps + Pd+ Pe. Note that thereactive powers, which are usually present in a system and circulate stored energy aroundit, cancel at resonance (which can be proven for example in electromagnetism from Poyn-tings Theorem [14]) and do not influence the power-balance calculations. The working effi-ciency is then:

gwork Pwork

Ptotal 1

1 CdeCwork

1 1fom2e

1 CworkCde

2 ; 4



13/15

where fome je=ffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiCseCde

pis the distance-dependent figure-of-merit of the perturbed

resonant energy-exchange system. Depending on the targeted application, reasonablechoices for the work-drainage rate are: Cwork/Cd[e] = 1 to minimize the required energy

stored in the source, Cwork=Cde ffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi1 fom

2

eq > 1 to maximize the efficiency for someparticular value of fom[e] or Cwork/Cd[e] ) 1 to minimize the required energy stored inthe device. For any of these choices, gwork is a function of the fom[e] parameter only. gworkis shown for its optimal choice in Fig. 7 with a solid black line, and is gwork > 17% forfom[e] > 1, namely large enough for practical applications. The loss conversion ratios de-pend also on the other system parameters, and the most disturbing ones (radiation andabsorption in stray objects) are plotted in Fig. 7 for the two example systems of dielectricdisks and conducting loops with values for their parameters within the ranges determinedearlier.

To get a numerical estimate for a system performance, take, for example, coupling dis-

tance D/r = 5, a human extraneous object at distance Dh/r = 10, and that Pwork = 10 Wmust be delivered to the load. Then, for dielectric disks we have (based on Fig. 5)Qradsh Qraddh $ 103, Qabss Qabsd $ 104, Qabssh Qabsdh $ 5 104 and (based on Figs. 2 and6) fom[h] $ 3, so from Fig. 7 we find efficiency gwork = 52% and that Prad % 8.3 W will

.1 .2 .3 .5 1 2 3 5 10 20 30 50 1000

0.1

0.2

0.3

0.4

0.5

0.6

0.7

0.8

0.9

1

fom[e]

= [e]/(

s[e]d[e]

)1/2

conversionr

atios

(efficiencies)

Qedecreases

Qedecreases

efficiency

work

radiation lossfor dielectric disks

absorption loss in e

for dielectric disks

radiation loss

for conducting loops

Fig. 7. Black line. Efficiency of converting the supplied power into useful work (gwork) as a function of theperturbed coupling-to-loss figure-of-merit, optimized with respect to the power-extracting rate Cwork (related tothe load impedance), for all values of the various quality factors that are present in the system. Blue and red lines.Ratios of power conversion respectively into radiation (including scattering from nearby extraneous objects) and

dissipation inside an extraneous object as a function of the figure-of-merit for dielectric disks ofQrad

se Qrad

de $ 103

and Qabss Qabsd $ 104, and for three values of Qabsse Qabsde 104; 5 104; 105. Green line. Ratio of powerconversion into radiation for conducting-wire loops ofQradse Qradde $ 104 and Qabss Qabsd $ 103, and assumingQabsse Qabsde ! 1. (For interpretation of the references to color in this figure legend, the reader is referred to theweb version of this paper.)



14/15

be radiated to free space, Ps % 0.5 W will be dissipated inside the source, Pd% 0.3 W insidethe device, and Ph % 0.2 W inside the human. On the other hand, for conducting loops wehave (based on Figs. 3 and 4) Qradsh Qraddh $ 104, Qabss Qabsd $ 103, Qabssh Qabsdh ! 1 andfom[h]

$4, so we find gwork = 61%, Prad

%0.6 W, Ps

%3.6 W, Pd

%2.2 W, and most

importantly Phfi 0.

5. Conclusion

In conclusion, we present a scheme based on strongly-coupled resonances for mid-range wireless non-radiative energy transfer. Although our consideration has been for astatic geometry (namely j and Ce were independent of time), all the results can be applieddirectly for the dynamic geometries of mobile objects, since the energy-transfer time j1

($1100 ls for microwave applications) is much shorter than any timescale associatedwith motions of macroscopic objects. Analyses of very simple implementation geometriesprovide encouraging performance characteristics and further improvement is expectedwith serious design optimization. Thus the proposed mechanism is promising for manymodern applications. For example, in the macroscopic world, this scheme could poten-tially be used to deliver power to robots and/or computers in a factory room, or electricbuses on a highway (source-cavity would in this case be a pipe running above the high-way). In the microscopic world, where much smaller wavelengths would be used and smal-ler powers are needed, one could use it to implement optical inter-connects for CMOSelectronics, or to transfer energy to autonomous nano-objects (e.g. MEMS or nano-robots) without worrying much about the relative alignment between the sources and

the devices.As a venue of future scientific research, enhanced performance should be pursued forelectromagnetic systems either by exploring different materials, such as plasmonic or met-allodielectric structures of large effective refractive index, or by fine-tuning the systemdesign, for example by exploiting the earlier mentioned interference effects between theradiation fields of the coupled objects. Furthermore, the range of applicability could beextended to acoustic systems, where the source and device are connected via a commoncondensed-matter object.

Acknowledgments

We thank Prof. John Pendry and L.J. Radziemski for suggesting magnetic and acousticresonances respectively, and Prof. Steven G. Johnson, Prof. Peter Fisher, Andre Kurs andMilos Popovic for useful discussions. This work was supported in part by the MaterialsResearch Science and Engineering Center program of the National Science Foundationunder Grant No. DMR 02-13282, by the US Department of Energy under Grant No.DE-FG02-99ER45778, and by the Army Research Office through the Institute for SoldierNanotechnologies under Contract No. DAAD-19-02-D0002.

References

[1] N. Tesla, Apparatus for transmitting electrical energy, US patent number 1,119,732, issued in December 1914.[2] J.M. Fernandez, and J.A. Borras, Contactless battery charger with wireless control link, US patent number

6,184,651, issued in February 2001.



15/15

[3] L. Ka-Lai, J.W. Hay, and P.G.W. Beart, Contact-less power transfer, US patent number 7,042,196, issued inMay 2006 (SplashPower Ltd., ).

[4] A. Esser, H.-C. Skudelny, IEEE Trans. Industry Appl. 27 (1991) 872.[5] J. Hirai, T.-W. Kim, A. Kawamura, IEEE Trans. Power Electron. 15 (2000) 21.[6] G. Scheible, B. Smailus, M. Klaus, K. Garrels, and L. Heinemann, System for wirelessly supplying a large

number of actuators of a machine with electrical power. US patent number 6,597,076, issued in July 2003(ABB, ).

[7] A. Takao et al., Nature 443 (2006) 671.[8] H.A. Haus, Waves and Fields in Optoelectronics, Prentice-Hall, New Jersey, 1984.[9] D.M. Pozar, Microwave Engineering, Wiley, New Jersey, 2005.

[10] M.V. Jacob, Proc. IEEE TENCON 2003 4 (2003) 1362.[11] H. Raether, Surface Plasmons, Springer-Verlag, Berlin, 1988.[12] D.F. Sievenpiper et al., Phys. Rev. Lett. 80 (1998) 2829.[13] COMSOL Inc. ().[14] J.D. Jackson, Classical Electrodynamics, Wiley, New York, 1999.[15] C.A. Balanis, Antenna Theory: Analysis and Design, Wiley, New Jersey, 2005.

[16] K. Fenske, D.K. Misra, Appl. Microw. Wireless 12 (2000) 92.

http://www.splashpower.com/http://www.abb.com/http://www.comsol.com/http://www.comsol.com/http://www.abb.com/http://www.splashpower.com/

Wireless Power AoP

Documents

Transcript of Wireless Power AoP