Transistor and Circuit Design for 100-200 GHz ICs [email protected] 805-893-3244, 805-893-5705...
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Transcript of Transistor and Circuit Design for 100-200 GHz ICs [email protected] 805-893-3244, 805-893-5705...
Transistor and Circuit Design for 100-200 GHz ICs
[email protected] 805-893-3244, 805-893-5705 fax
Mark Rodwell University of California, Santa Barbara
V. Paidi, Z. Griffith, D. Scott, Y. Dong, M. Dahlström, Y. Wei, N. ParthasarathyUniversity of California, Santa Barbara
Lorene Samoska, Andy FungJet Propulsion Laboratories
M. Urteaga, R. Pierson , P. Rowell, B. BrarRockwell Scientific Company
S. Lee, N. Nguyen, and C. NguyenGlobal Communication Semiconductors
2004 IEEE Compound Semiconductor IC Symposium, October, Monterey
Potential applications for 100-300 GHz Electronics
Optical Fiber Transmission
40 Gb/s: InP and SiGe ICs commercially available
80 & 160 Gb/s is feasible80-160 Gb/s InP ICs now clearly feasible ~100 GHz modulators demonstrated (KTH Stockholm)100 + GHz photodiodes demonstrated in 1980'schallenge: limit to range due to fiber dispersionchallenge: competition with WDM using 10 Gb CMOS ICs
Radio-wave Transmission / Radar / Imaging
65-80 GHz, 120-160 GHz, 220-300 GHz100 Gb/s transmission over 1 km in heavy rain300 GHz imaging for foul-weather aviation
sciencespectroscopy, radio astronomy
Mixed-Signal ICs for Military Radar/Comms
direct digital frequency synthesis, ADCs, DACshigh resolution at very high bandwidths sought
40 Gb/s InP HBT fiber chip set (Gtran Inc.)
100 Gb/s over 1 km in heavy rain : 250 GHz carrier
300 GHz imagining radar for foul-weather aviation
Fast IC Technologies
InP HBT:
Advantages 3.5x107 cm/s collector velocity 500 Ohm/square base sheet
Performance 500 nm scaling generation: 400 GHz f / 500 GHz fmax
4 V breakdown 150 GHz static dividers 178 GHz amplifiers
Comments scaling will improve bandwidth scaling can reduce power small market <-> high cost
SiGe HBT:
Advantages superior scaling extrinsic parasitic reduction CMOS integration
Performance 130 nm scaling generation: 210 GHz f / 270GHz fmax
96 GHz static dividers 77 GHz amplifiers 150 GHz push-push VCO- 75 GHz fundamental
SOI CMOS:
Advantages cost, power, integration scales
Performance 90 nm scaling generation: ~200 GHz f & fmax
60 GHz 2:1 mux 91 GHz amplifiers
Optical Transmitters / Receivers are Mixed-Signal ICs
TIA: small-signal
aa
routebuffer
SwitchWideband Optical Transceiver
clockPLL
AD
DMUX
O/E, E/O interfaces
MUX
AD
AD
IQ
I
Q
DMUX
DMUX
mm-wave interfaces
I
Q
DA
DA
IQ
electronicor optical
Wideband mm-Wave Transceiver
Electronics for GigaHertz Communication
poweramplifier
MUX
addressdetect
PLL
Switches:network protocols,digital control, fast ICs,optical, electronic switches
Rf
Rc
Q1
Q2
I1
I2
Rf
Rc
Q1
Q2
I1
I2
LIA: often limiting MUX/CMU & DMUX/CDR:mostly digital
Small-signal cutoff frequencies (ft , fmax) are ~ predictive of analog speed
Limiting and digital speed much more strongly determined by I/C ratios
We design HBTs for low gate delay, not for high f & fmax
clock clock clock clock
inin
out
out
cexLOGIC
LOGIC
Ccb
becbi
becbC
LOGIC
IRq
kTV
V
IR
CCR
CCI
V
4
leastat bemust swing logic The
resistance base the through
charge stored
collector base Supplying
resistance base the through
charging ecapacitanc on Depleti
swing logic the through
charging ecapacitanc on Depleti
:by ermined Delay DetGate
bb
depletion,bb
depletion,
JVR
v
T
A
A
V
V
I
VC
T)V(VvεJ
CI
CCIV
f
ex
electron
C
CE
LOGIC
C
LOGICcb
cceceelectronKirk
cbC
becbCLOGIC
cb
highat low for low very bemust
22
/2
objective. design key HBTa is / High
total.of 80%-55% is
withcorrelated not well Delay
delay; totalof 25%-10y typicall)(
logic
emitter
collector
min,
2depletion full,operating ,max,
depl,
1:10~ is which ,/
of ratioby reduced
ecapacitancdiffusion signal-Large
)(
)(Q
:Operation Signal-LargeUnder
swing. voltage/over only ...active
/
)(
)(
)(Q
:ecapacitancDiffusion
base
base
qkT
V
VV
I
I
qkT
VqkT
I
VdV
dI
I
LOGIC
LOGICLOGIC
dccb
Ccb
beCcb
bebe
Ccb
Ccb
Why isn't base+collector transit time so important for logic?
Depletion capacitances present over full voltage swing, no large-signal reduction
Vin
Vout
Vin(t)
t
t
Vout(t)
diffusion+ depletioncapacitance
only depletioncapacitance
Scaling Laws, Collector Current Density, Ccb charging time
Collector Field Collapse (Kirk Effect)
Collector Depletion Layer Collapse
)2/)(/( 2 cdsatcb TqNvJV
)2/)(( 2min, cTqNV dcb
0 mA/m2
10 mA/m2
0 mA/m2
10 mA/m2
GaAsSb base InGaAs base
sat
C
CECE
LOGICCLOGICcCLOGICcb v
T
A
A
VV
VIVTAIVC
2/
emitter
collector
min,collector
2min,max /)2(2 ccbcbsat TVVvJ
cecbbe VVV )( hence , that Note
Collector capacitance charging time scales linearly with collector thickness if J = Jmax
.1 where; 2max,
emitter
logiccollectorlogicce
eCCcb /TJ
AJ
V
T
εA
I
VC
ex 7 m2 needed for 200 GHz clock rate
ECL delay not well correlated with f or fmax
Key HBT Scaling Limit Emitter Resistance
Io
RL
Rex
Noise margin
2kT/q+IoRex
Vin
Vout
Vlogic=IoRL
Vlogic
Largest delay is charging Ccb
Je 10 mA/m2 needed for 200 GHz clock rate
Voltage drop of emitter resistance becomes excessive
RexIc = exJe = (15 m2) (10 mA/m2) = 150 mV
considerable fraction of Vlogic 300 mV
Degrades logic noise margin
Breakdown: Thermal failure is more significant than BVCEO
0
2
4
6
8
10
12
0 1 2 3 4 5 6
device failure
18 mW/um2
design limit 10 mW/um 2
J max
(m
A/u
m2)
Vce
(V)
8 m emitter metal length, ~0.6 m junction width
biased without failure (DC-IV)
No RF driftafter 3-hr burn-in ECL
bias points
0
2
4
6
8
10
12
14
0 1 2 3 4 5 6 7 8
J e (m
A/
m2 )
Vce
(V)
Ajbe
=0.6 x 7 m2 Ib step
= 0.4 mA0.5 um X 7 um emitter junction0.5 um base contact width
~6.8 V low-currentBVCEO
resistance lmW therma/m)( K7~ 2
2max
2
/1
densitypower limits nDissipatio
clockja
CEclockceEE
fV
VfVJAP
collectors thin withincreases because
nslowly tha more decreases
relevantnot often breakdowncurrent -low
high requires and High
low at measured is -or -Breakdown
max
1collectormax,
max
,,
E
fTEV
Jff
JVV
clockceobr
e
ecbobrceobr
Low thermal resistance is critical.DHBTs are superior to SHBTs.
Bipolar Transistor Scaling Laws & Scaling Roadmaps
key device parameter required change
collector depletion layer thickness decrease 2:1
base thickness decrease 1.414:1
emitter junction width decrease 4:1
collector junction width decrease 4:1
emitter resistance per unit emitter area decrease 4:1
current density increase 4:1
base contact resistivity (if contacts lie above collector junction)
decrease 4:1
base contact resistivity (if contacts do not lie above collector junction)
unchanged
Scaling Laws:design changes required to double transistor bandwidth
WE
WBC
WEB
x
L E
base
emitter
base
collector
WC
InP Technology Roadmap 40 / 80 / 160 Gb/s digital clock rate
Key scaling challengesemitter & base contact resistivitycurrent density→ device heatingcollector-base junction width scaling & Yeild !
key figures of merit
for logic speed
InP DHBTs: 600 nm emitter width, 150 nm thick collector
0
5
10
15
20
25
30
35
109 1010 1011 1012
Gai
ns
(dB
)
Frequency (Hz)
ft = 391 GHz, f
max = 505 GHz
U
H21
Ic = 13.2 mA
Ajbe
= 0.6 x 4.25 um2
Je = 5.17 mA/um2, V
cb= 0.6 V
200
300
400
500
1 2 3 4 5 6
GH
z
Je (mA/um2)
ft
fmax
Vcb
= 0.6 V
10-12
10-10
10-8
10-6
10-4
0.01
0 0.2 0.4 0.6 0.8 1
I b, I
c (A
)
Vbe
(V)
VCB
= 0.3 V
Ic
Ib
nc = 1.17
nb = 1.38
0
1
2
3
4
5
6
7
0.0 0.5 1.0 1.5 2.0 2.5
J e (m
A/
m2 )
Vce
(V)
Ib step
= 85 uA
Peak ft, f
max
391 GHz f , 505 GHz fmax
Zach Griffith
setback
grad
e
base
emitt
er
InP
colle
ctor
Ccb/Ic ~0.5 ps/V
+V +V +V
0V
kz
Microstrip mode Substrate modes
+V
0VCPW mode
0V 0V
CPW has parasitic modes, coupling from poor ground plane integrity
kz
Microstrip has high via inductance, has mode coupling unless substrate is thin.
We prefer (credit to NTT) thin-film microstrip wiring, inverted is best for complex ICs
-V 0V +V
0VSlot mode
ground straps suppress slot mode, but multiple ground breaks in complex ICs produce ground return inductanceground vias suppress microstrip mode, wafer thinning suppresses substrate modes
M. Urteaga, Z. Griffith, S. Krishnan
unitsdata
current steering
data emitter
followers
clock current steering
clock emitter
followerssize m2 0.5 x 3.5 0.5 x 4.5 0.5 x 4.5 0.5 x 5.5
currentdensity
mA/m2 6.9 4.4 4.4 4.4
Ccb/Ic psec / V 0.59 0.99 0.74 0.86
Vcb V 0.6 0 0.6 1.7
f GHz 301 260 301 280
fmax GHz 358 268 358 280
UCSB / RSC / GCS 150 GHz Static Frequency Dividers
-40
-30
-20
-10
0
10
20
0 20 40 60 80 100 120 140 160
Min
imu
m in
put
pow
er (
dBm
)
frequency (GHz)
IC design: Zach Griffith, UCSBHBT design: RSC / UCSB / GCSIC Process / Fabrication: GCSTest: UCSB / RSC / Mayo
-80
-70
-60
-50
-40
-30
74.9975 74.9987 75.0000 75.0012 75.0025
Out
put
Pow
er (
dB
m)
frequency (GHz)
-90
-80
-70
-60
-50
-40
-30
-20
-10
0.00 19.00 38.00 57.00 76.00
Out
put
Pow
er (
dB
m)
frequency (GHz)
probe station chuck @ 25C
PDC,total = 659.8 mWdivider core without output buffer 594.7 mW
UCSB 142 GHz Master-Slave Latches (Static Frequency Dividers)
-90
-80
-70
-60
-50
-40
-30
-20
-10
0.0 15.0 30.0 45.0 60.0 75.0
Out
put
Pow
er (
dB
m)
frequency (GHz)
Static 2:1 divider:Standard digital benchmark.Master-slave latch with inverting feedback.Performance comparison between digital technologies
UCSB technology 2004:InP mesa HBT technology12-mask process600 nm emitter width142 GHz maximum clock.
Implications:
160 Gb/s fiber ICs
100 + Gb/s serial links
Target is 260 GHz clock rate at 300 nm scaling generation
Z. Griffith, M. Dahlström
25o C
Reducing Divide-by-2 Dissipation
ECL with impedance-matched 50 Ohm bus:25 Ohm load→ switch 12 mA 12 mA x 7 x 4 V = 336 mW/latch
CML with impedance-matched 50 Ohm bus:25 Ohm load→ switch 12 mA 12 mA x 3 x 3 V = 108 mW/latch
Low-Power CML100 Ohm loaded → switch 3 mA 3 mA x 3 x 3 V = 27 mW/latch
What parts of circuit are included in stated dissipation ?
12 mA12 mA 12 mA
50 Ohm bus 50 Ohm 50 Ohm
12 mA
50 Ohm bus 50 Ohm 50 Ohm
50 Ohm bus100 Ohm
3 mA
3 mA 3 mA
padcbwiring CC ,low ,low power low @ speed High
7.5 mW output power
Mesa DHBT Power Amplifiers for 100-200 GHz Communications
7 dB gain measured @ 175 GHz
175 GHz Power Amplifier Demonstrated in a 300 GHz fmax process500 GHz fmax DHBTs available now, 600 GHz should be feasible soon
→ feasibility of power amplifiers to 350 GHz→ Ultra high frequency communications
2 fingers x 0.8 um x 12 um, ~250 GHz f, 300 GHz fmax , Vbr ~ 7V, ~ 3 mA/um2 current density
V. Paidi, Z. Griffith, M. Dahlström
172 GHz Common-Base Power Amplifier
8.3 dBm saturated output power 4.5-dB associated power gain at 172 GHz DC bias: Ic=47 mA, Vcb=2.1V.
-10
-5
0
5
10
140 150 160 170 180 190
S2
1,S1
1,S2
2, dB
Frequency, GHz
S11
S22
S21
RLVin Vout
Input Matching Network Output Loadline Match
-10
-5
0
5
10
15
0
1
2
3
4
5
-15 -10 -5 0 5
Gai
n,
dB
, O
utpu
t P
ower
, dB
m
PA
E (%
)
Input Power, dBm
Gain
Output Power
PAE
V. Paidi, Z. Griffith, M. Dahlström
6 dB gain
176 GHz Two-Stage Amplifier
7-dB gain at 176 GHz8.1 dBm output power, 6.3 dB power gain at 176 GHz9.1 dBm saturated output power at 176 GHz
-10
-5
0
5
10
15
140 150 160 170 180 190 200
S2
1,
S1
1,
S2
2 d
B
Frequency, GHz
S21
S11
S22
0
2
4
6
8
10
0
1
2
3
4
5
-6 -4 -2 0 2 4 6 8 10
Gai
n, d
B, O
utpu
t Pow
er ,
dBm
PA
E (%
)
Input Power, dBm
PAEGain
Output Power
RLVoutVin
50 Ohms 50 Ohms
InputMatchingNetwork
OutputLoadlineMatchingNetwork
InputMatchingNetwork
OutputLoadlineMatchingNetwork
at f0
at f0
Veb,bias
Vcb,bias
V. Paidi, Z. Griffith, M. Dahlström
InP HBT limits to yield: non-planar process
Yield quickly degrades as emitters arescaled to submicron dimensions
base contact
liftoff failure:emitter-baseshort-circuit
S.I. substrate
base
sub collector
base contact
excessiveemitter undercut
S.I. substrate
base
sub collector
S.I. substrate
base
sub collector
planarization failure: interconnect breaks
Griffith, Dahlström
Parasitic Reduction for Improved InP HBT Bandwidth
SiO2 SiO2
P base
N+ subcollector
N-thick extrinsic base : low resistancethin intrinsic base: low transit time
wide emitter contact: low resistancenarrow emitter junction: scaling (low Rbb/Ae)
wide base contacts: low resistancenarrow collector junction: low capacitance
At a given scaling generation, intelligent choice of device geometry reduces extrinsic parasitics
Much more fully developed in Si…
W
r
LR bulk
bulk
2ln
2
LrR c
contact 2
These are planar approximations toradial contacts:
extrinsic base
extrinsicemitter
N+ subcollector
extrinsic base
bulk
contactbulk
WLR
ln34.12
mintotal,
→ greatly reduced access resistance
UCSB/RSC/GCS TFAST HBT Technology Development
•High performance, low yield technology
•Difficult to scale to WE < 0.4 um
•Processed for epitaxy and circuit validation
Scaled mesa-HBT
S3 Technology
•Improved base-emitter process flow
•Process scalable to WE < 0.25 um
•Process modules that can be added to HBT technology
•Emitter regrowth for high yield, low Re
•Extrinsic base for low Rbb
•Pedestal implant for reduced Ccb
•Allows continued scaling even if base & emitter contact resistivities do not improve.
Regrowth Technology
S.I. InP
N+ Subcollector
N- collector
extrinsic basebase contact
regrown emitteremitter contact
SixNy
collectorcontact
intrinsic base
Low Parasitic, Scalable HBT processes
Collector pedestal implant
N- collector
N+ subcollector
S.I. substrate
collectorpedestal
Extrinsic emitter regrowthEmitter sidewall process
high-yield (10,000 transistor)alternative to emitter-base definition by mesa etch
SiGe-like emitter-base processwide emitter contact → low resistancethick extrinsic base → low resistance
Independent control of base contact & collector junction widths → reduced capacitance
15
20
25
30
35
0 1 2 3 4 5 6 7 8
Ccb
(fF
)
Je (mA/m2)
Aje = 0.5 x 7 m2
Vcb
= 0.3 V2.1 m collector pedestal
1.2 m collector pedestal
1.0 m collector pedestal
0
5
10
15
20
25
30
1 10 100 1000
IC=9.72 mA
VCE
=1.2 V
U,
MS
G/M
AG
, h 21
(dB
), K
Frequency (GHz)
U
h21MAG/MSG
K
fT=280 GHzf
MAX=148GHz
Emitter junction area: 0.3 x 4 m2
-2.00
0.00
2.00
4.00
6.00
8.00
10.00
12.00
14.00
16.00
18.00
0.00 0.50 1.00 1.50 2.00 2.50
Vce (V)
Ic (
mA
)
Miguel Urteaga
Dennis Scott, Yun Wei
RSC/GCS/UCSBVitesse similar to earlier Hitachi, NEC, NTT GaAs HBT processes
RSC/GCS/UCSBNorthrup Grumman
RSC/GCS/UCSBHRL Labs
Yingda Dong
Collector Pedestal Implant for InP HBTs
Pedestal can be integrated into: sidewall or mesa emitter processes, emitter regrowth process
0 1 2 3 4 5 6 7 815
20
25
30
35
AE=0.7 x 8 um2
1.0 um pedestal
1.2um pedestal
2.1um pedestal
CC
B (
fF)
JE (mA / um2)
~2:1 reduction in collector base capacitance
Good DC characteristics, high power density,increased breakdown: 5.4 V with a 90 nm thick collector
N++ InP subcollector
Collector contact
N+ pedestalBase contact
Emitter contact
SI substrate
N- collector UID InP
0
2
4
6
8
10
0 1 2 3 4 5 6
J e (
mA
/m
2)
Vce
(V)
Aje = 0.4 x 7 m2
Ib step = 500 A
HBT with pedestalHBT without pedestal
20 mW/m2 device failure
large collector capacitance reductionsignificant increase in breakdown2(1013) V-sec Johnson Figure-of-Merit transistors have low leakage, good DC characteristics
Y. Dong et. al.:ISDRC December 2003,DRC June 2004
What's next ? 250 nm Scaling Generation for >200 GHz clock
sidewall processes for 300 nm at high yield
narrow collector junctions needed low contact resistivity modified sidewall spacer process &/or collector pedestal
power density near reliability limits narrow emitters should improve heatsinking
Decreasing Acollector/Aemitter decreases required Je
eases thermal design
Indium Phosphide HBTs for 100-200 GHz ICsInP HBT: high speed & room left to scale 150 GHz digital clock (static divider) at 500 nm scaling generation 210 GHz clock should soon be feasible at 250 nm scaling. low NRE; low mask cost
Applications feasible soon: 160 Gb fiber ICs, 300 GHz MIMICs for communications & radar GHz mixed-signal ICs for radar & communications
Planar processes address yield limitations emitter-base junction: liftoff-free dielectric sidewall process base-collector junction: planar implanted process
Volume markets are needed to drive down cost GaAs HBT power amplifier processes are cheap Why can't InP HBT be inexpensive ? InP HBT can be scaled at high yieldKey to survival of the technology are emergence of singificant markets progress relative to CMOS & InP