Page 1AES Brief – 25-Mar-03 TDR Spatial Array Digital Beamforming and Filtering L-3 Communications...
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Transcript of Page 1AES Brief – 25-Mar-03 TDR Spatial Array Digital Beamforming and Filtering L-3 Communications...
Page 1AES Brief – 25-Mar-03 TDR
Spatial Array Digital Beamforming and Filtering
L-3 Communications Integrated SystemsGarland, Texas972.205.8411
Tim D. Reichard, M.S.
Page 2AES Brief – 25-Mar-03 TDR
Spatial Array Digital Beamforming and Filtering
OUTLINE
• Propagating Plane Waves Overview
• Processing Domains
• Types of Arrays and the Co-Array Function
• Delay and Sum Beamforming
– Narrowband– Broadband
• Spatial Sampling
• Minimum Variance Beamforming
• Adaptive Beamforming and Interference Nulling
• Some System Applications and General Design Considerations
• Summary
Page 3AES Brief – 25-Mar-03 TDR
Propagating Plane Waves
k
Temporal Freq. Spatial Freq. (|k| = )
s(xo,t) = Ae j(t - k . xo)
Monochromatic Plane Wave (far-field):
k = Wavenumber Vector = direction of propagation
x = Sensor position vector where wave is observed
x
Using Maxwell’s equations on an E-M field in free space, the Wave Equation is defined as:
2s + 2s + 2s = 1 . 2sx2 y2 z2 c2 t2
• Governs how signals pass from a radiating source to a sensing array
• Linear - so many plane waves in differing directions can exist simultaneously => the Superposition Principal
• Planes of constant phase such that movement of x over time t is constant
• Speed of propagation for a lossless medium is |x|/t = c
• Slowness vector: = k/ and || = 1/c
• Sensor placed at the origin has only a temporal frequency relation:
s([0,0,0], t) = Ae jt
Notation: Lowercase Underline indicates 1-D matrix (k) Uppercase Underline indicates 2-D matrix (R) or H indicates matrix conjugate-transpose
Page 4AES Brief – 25-Mar-03 TDR
Processing Domains
Space-Time
s(x, t) = s(t - . x)s(x, t)
Space-Freq
S(x, )
e-jt
ejt
Wavenumber -Frequency
S(k, )
(or beamspace)
e-jk.x
ejk.x
Wavenumber -Time
S(k, t)
ejt
e-jt
e-jk.x
ejk.x
Page 5AES Brief – 25-Mar-03 TDR
Some Array Types and the Co-Array Function
2-D Array
d
x
Uniform Linear Array (ULA)
m= 0 1 2 3 4 5 6
dorigin
x
M = 7
Sparse Linear Array (SLA)
m= 0 1 2 3
d x
M = 4
Co-Array Function:
C() = wm1w*m2
where; m1 and m2 are a set of indices for xm2 – xm1 =
- Desire to minimize redundancies and- Choose spacing to prevent aliasing
m1,m2
x 0 1d 2d 3d 4d 5d 6d
Co-Array
# Redundancies
6
2
4
x 0 1d 2d 3d 4d 5d 6d
# Redundancies4
1
2
3Co-Array “A Perfect Array”
Page 6AES Brief – 25-Mar-03 TDR
Delay and Sum Beamformer (Narrowband)
Delay0
Delay1
DelayM-1
w*0
w*1
w*M-1
.
.
.
y0(t)
y1(t)
yM-1(t)
.
.
.
z(t)
z(t) = w*m ym(t - m) = ejot w*m e-j(om + ko . xm) = wHy
M-1
m=0
Time Domain: M-1
m=0
ko
s(x,t) = e j(ot - ko . x)
Freq Domain:
Z() = w*mYm(xm) e-j(om) = w*mYm(xm) ej(ko . xm) = eHWY
M-1
m=0 m=0
M-1
e is a Mx1 steering vector -||ko||let m = (-||ko|| . xm) / c
Page 7AES Brief – 25-Mar-03 TDR
Delay and Sum Beamformer (Broadband)
z(n)
.
.
.
z(n) = w*m,p ym(n - p) = wHy(n) m=1
J
y1(n)
w*1,0
z-1
w*1,1
z-1 z-1
w*1,L-1. . .y2(n)
w*2,0
z-1
w*2,1
z-1 z-1
w*2,L-1. . .
...
...
yJ(n)
w*J,0
z-1
w*J,1
z-1 z-1
w*J,L-1. . .
...
L-1
p=0
J = number of sensor channels
L = number of FIR filter tap weights
Page 8AES Brief – 25-Mar-03 TDR
Spatial Sampling
I
LPF(/I)
y0(n) u’0(n) w0
Delay0
I
y1(n)z(n)
w1
Delay1
I
yM-1(n) u’M-1(n) wM-1
DelayM-1
.
.
.I
Up-sample
Down-sample
M-Sensor ULA Interpolation Beamformer (at location xo):
z(n) = wm ym(k) * h((n-k)T-m)m=0
M-1
k
.
.
.
• Motivation: Reduce aberrations introduced by delay quantization
• Postbeamforming interpolation is illustrated with polyphase filter
Page 9AES Brief – 25-Mar-03 TDR
Minimum Variance (MV) Beamformer
• Apply a weight vector w to sensor outputs to emphasize a steered direction () while
suppressing other directions such that at = o: Real {ew} = 1
Hence: min E[ |wy|2] yields => wopt = R-1 e / [eR-1e ]
Conventional (Delay & Sum Beamformer) Steered Response Power:
PCONV(e) = [ eWY ] [ YWe ] = eR e for unity weights
Minimum Variance Steered Response Power:
PMV(e) = woptR wopt = [eR-1e ]-1
w
• MVBF weights adjust as the steering vector changes
• Beampattern varies according to SNR of incoming signals
• Sidelobe structure can produce nulls where other signal(s) may be present
• MVBF provides “excellent” signal resolution wrt steered beam over the
Conventional Delay & Sum beamformer
• MVBF direction estimation accuracy for a given signal increases as SNR increases
R = spatial correlation matrix = YY
Page 10AES Brief – 25-Mar-03 TDR
ULA Beamformer Comparison
PMV() =
[e(R-1 e()]-1
PCONV() =
[e(R e()]
; = o
Page 11AES Brief – 25-Mar-03 TDR
Adaptive Beamformer Example #1 - Frost GSC Architecture
• For Minimum Variance let C = e, c = 1
• e = Array Steering Vector cued to SOI
• R is Spatial Correlation Matrix = y(l)y(l)
• Rideal= ss + I2 = Signal Est. + Noise Est.
• Determine Step Size () using Rideal:
= 0.1*(3*trace[PRidealP])-1
• P = I - C(CC)-1C
• wc = C(CC)-1c
• w(l=0) = wc
Constrained Optimization:
min wRw subject to Cw = c
Setup:
• z(l) = w(l)y(l)
• w(l+1) = wc + P[w(l) - z*(l)y(l)]
Adaptive (Iterative) Portion:
No
n-A
dap
tive
w
c AdaptiveAlgorithm
y0(l)
y1(l)
z(l)
yM-1(l)
.
.
.
Ad
apti
ve
w
w
Frost GSC†
.
.
.
.
.
.
†- General Sidelobe Canceller
Page 12AES Brief – 25-Mar-03 TDR
Example Scenario for a Digital Minimum Variance Beamformer
Signal of Interest (SOI) location
Beam Steered to SOI with 0.4 degree pointing error
Coherent Interference Signal(7 deg away & 5dB down from SOI)
Shows Signals Resolvable
• N = 500 samples• M = 9 sensors, ULA with d = /2 spacing• SOI pulse present in samples 100 to 300• Co-Interference pulse present in samples 250 to 450
Setup Info used:
• Aperture Size (D) = 8d• Array Gain = M for unity wm m
W(k) = wmej(k.x)m=0
M-1
PMV() =
[e(R-1e()]-1
Page 13AES Brief – 25-Mar-03 TDR
Example of Frost GSC Adaptive Beamformer Performance Results†
†- via Matlab simulation
Page 14AES Brief – 25-Mar-03 TDR
Adaptive Beamformer Example #2 - Robust GSC Architecture
Constrained Optimization:
min wRw subject to Cw = c and ||Bwa||2 < 2 - ||wc||2
where is constraint placed on adapted weight vectorSetup:
• For Minimum Variance let C = e, c = 1
• e = Array Steering Vector cued to SOI
• B is Blocking Matrix such that BC = 0
• Determine Step Size () using Rideal:
= 0.1*(max BRidealB)-1
• wa = Bwa
• wc = C(CC)-1c
~
• yB(l) = By(l)
• v(l) = wa(l) + z*(l)B yB(l)
• wa(l+1) = v(l), ||v(l)||2 < 2 - ||wc||2
(2-||wc||2)1/2 v(l)/||v(l)||, otherwise
• z(l) = [wc - wa(l)]y(l)
Adaptive (Iterative) Portion:
~
~
~
LMSAlgorithm
y0(l)
y1(l)
yM-1(l)
.
.
.
Robust GSC
Delay0
Delay1
DelayM-1
w*c(0)
w*c(1)
w*c(M-1)
+
B...
w*a,M-1(l)
w*a,0(l)
z(l)
_
wa
wa~
.
.
.
Page 15AES Brief – 25-Mar-03 TDR
Example of Robust GSC Adaptive Beamformer Performance Results†
†- via Matlab simulation
Page 16AES Brief – 25-Mar-03 TDR
Adaptive Beamformer Relative Performance Comparisons
• SOI Pulsewidth retained for both; Robust has better response• Robust method’s blocking matrix isolates adaptive weighting to nonsteered response• Good phase error response for the filtered beamformer results• Amplitude reductions due to contributions from array pattern and adaptive portions• The larger the step size (), the faster the adaptation• Additional constraints can be used with these algorithms
• min PRP is proportional to noise variance => adaptation rate is roughly proportional to SNR
RMS Phase Noise = 136 mrad
RMS Phase Error = 32 mrad
Page 17AES Brief – 25-Mar-03 TDR
Applications to Passive Digital Receiver Systems
y0(t)
y1(t)
yM-1(t)
.
.
.
DCM Digitizer
DCM Digitizer
DCM Digitizer
Adaptive Beamformer
Signal Detection and
ParameterEncoding
BPF
BPF
BPF
S
tee
rin
g V
ec
tor
.
.
.
• Sparse Array useful for reducing FE hardware while attempting to retain aperture size -> spatial resolution
• Aperture Size (D) = 17d in case with d = /2 and sensor spacings of {0, d, 3d, 6d, 2d, 5d}
• Co-array computation used to verify no spatial aliasing for chosen sensor spacings
• Tradeoff less HW for slightly lower array gain
• Further reductions possible with subarray averaging at expense of beam-steering response and resolution performance
Page 18AES Brief – 25-Mar-03 TDR
Summary
• Digital beamforming provides additional flexibility for spatial filtering and suppression of unwanted signals, including coherent interferers
• Various types of arrays can be used to suit specific applications
• Minimum Variance beamforming provides excellent spatial resolution performance over conventional BF and adjusts according to SNR of incoming signals
• Adaptive algorithms, implemented iteratively can provide moderate to fast monopulse convergence and provide additional reduction of unwanted signals relative to user defined optimum constraints imposed on the design
• Adaptive, dynamic beamforming aids in retention of desired signal characteristics for accurate signal parameter measurements using both amplitude and complex phase information
• Linear Arrays can be utilized in many ways depending on application and performance priorities
Page 19AES Brief – 25-Mar-03 TDR
References
D. Johnson and D. Dudgeon, “Array Signal Processing Concepts and Techniques,” Prentice Hall, Upper Saddle River, NJ, 1993.
V. Madisetti and D. Williams, “The Digital Signal Processing Handbook,” CRC Press, Boca Raton, FL, 1998.
H.L. Van Trees, “Optimum Array Processing - Part IV of Detection, Estimation and Modulation Theory,” John Wiley & Sons Inc., New York, 2002.
J. Tsui, “Digital Techniques for Wideband Receivers - Second Edition,” Artech House, Norwood, MA, 2001.