Microwave Wireless Power Transmission Systemjaf35230/Microwave_Wireless_Power_Transmission… ·...
Transcript of Microwave Wireless Power Transmission Systemjaf35230/Microwave_Wireless_Power_Transmission… ·...
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Abstract—This paper discusses an implementation of a far-field
wireless power transmission system using microwaves in the ISM
band. In this project, antennas transmit and receive power at a
frequency of 2.45 GHz over distances up to more than 60 cm. The
design, fabrication, and testing of a microstrip patch array
antenna is illustrated in this paper. Furthermore, three different
rectifier designs are discussed and compared based on their
performance: a peak rectifier, a full-wave rectifier, and a voltage
doubler rectifier. Finally, this paper discusses the overall results of
the system including how input power and distance between
antennas affect the output voltage of the system. The entire system
is able to illuminate a light-emitting diode (LED) wirelessly at
maximum distance up to 40 cm between the antennas.
Keywords—RF; microwaves; ISM; antenna; microstrip patch;
rectifier; voltage doubler rectifier; full-wave rectifier; peak
rectifier.
I. INTRODUCTION
ireless power transmission has been a topic of research
interest for several decades. Many technology leaders are
investing substantially into this technology to be able to add
wireless charging capability to their devices. In general,
wireless power transmission technology falls into two
categories: near-field and far-field. In near-field technologies,
power is transferred wirelessly over short distances using
inductive coupling with coils. This category is widely used to
add wireless charging capabilities with charging mats to smart
phones and other handheld devices. However, techniques used
in this category can only transmit power over a very short
distance. On the other hand, in far-field technologies, power is
transferred via electromagnetic radiation such as microwaves
and laser beams. In contrast to near-field, far-field technologies
provide power transmission over much longer distances but
have considerable propagation losses.
This paper describes a far-field wireless power transmission
system. In this system, antennas transmit power using
microwaves in the ISM band. As shown in Fig. 1, a signal
generator will generate power at 2.45 GHz and will be
connected to a transmitter antenna which will transmit the
power using microwaves to the receiver antenna. The power
received at the receiver antenna will be connected to a rectifier
which will convert the received microwave signal into DC
power. Then, the converted DC power will be connected to a
load such as a light-emitting diode (LED). In Section II of this
paper, the transmitter and receiver antennas will be discussed,
while Section III will focus on the rectifier circuits tested in this
project. The overall system performance will be explored in
Section IV, followed by conclusion in Section V.
Fig. 1. Microwave wireless power transmission block diagram
To ensure safety from high-levels of electromagnetic
radiation, the system designed in this project is FCC (Federal
Communications Commission) compliant. Part 15 of
subchapter A in chapter 1 under title 47 of FCC
telecommunication rules and regulations shows the maximum
power that can be safely transmitted between the two antennas
[7]. For the gain of the antenna used in this project, 28 dBm is
the maximum power that can be safely transmitted which will
not be exceeded in this project. All the antennas and rectifier
circuits are home-built; thus, equipment authorization is not
required by FCC.
II. ANTENNA
To achieve our objective, which is transmitting power using
microwaves, a device was required that can transmit, receive
and handle a certain amount of power. In other words, an
antenna is required to achieve this objective. There are many
types of antennas such as dipoles, parabolic, and microstrip
patch antennas. Each one of them has its own features,
advantages and disadvantages. In this project, a microstrip
patch antenna was chosen because it has many advantages that
will help this project to be efficient. In particular, microstrip
patch antenna has a light weight and small size compared to
other antennas. Also, directivity is one of the most important
features of microstrip patch antenna. Directivity helps to
transmit maximum power possible into one direction.
Moreover, if considered fabricating the antenna with large
quantities, microstrip patch antenna has one of the lowest
fabricating costs [2].
Microwave Wireless Power Transmission
System
Omar Alsaleh, Yousef Alkharraz, Khaled Aldousari, Talal Mustafawi, and Abdullah Aljadi
Prof. Bradley Jackson
California State University, Northridge
November 16th, 2018
W
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A. Design
To design a microstrip patch antenna, different parameters
must be considered to design the antenna properly, as shown in
Fig. 2. The dielectric constant 𝜀𝑟 of the material used to
fabricate the antenna and the thickness of that material are not
free variables, so it has to be chosen before doing any
calculation. A lower dielectric constant will lead to a wider
impedance bandwidth. All of the parameters must be optimized
for the type and the height of the material.
Fig. 2. Microstrip patch antenna [3]
Considering the parameters shown in Fig.2, the width was
calculated using:
W =c
2𝑓√(εr+1)
2
where c is the velocity of electromagnetic waves in free space,
which equals to 3x1011 mm/s, and f is the operating frequency
in GHz. Then, the effective dielectric constant εreff was
calculated using:
εreff =εr + 1
2+εr − 1
2[1 + 12
h
W]−1
2
where 𝑊
ℎ>1. Finally, the length was calculated using:
L =c
2𝑓√εreff− 2∆L
where ∆𝐿 can be found using [3]:
∆L
h= 0.412
(εreff+0.3)(W
h+0.264)
(εreff−0.258)(W
h+0.8)
.
The microstrip patch antenna was designed to operate at 2.45
GHz. the parameters were calculated for that frequency using
the formulas mentioned earlier. The calculated parameters, as
shown in Table I, are approximated, and they must be optimized
with the simulator to have better results and the best reflection
coefficient possible. A reflection coefficient is the amount of
power reflected from the antenna, and it needs to be matched to
transmit or receive maximum power, where less than -10 dB is
considered well matched. The length of the patch will affect the
chosen operating frequency [1]. The geometry of the antenna is
shown in Fig. 3.
Fig. 3. Single microstrip patch antenna geometry
The single microstrip patch antenna has a gain around 7 dBi
and a reflection coefficient less than -10 dB between 2.42 GHz
and 2.47 GHz, as shown in Fig. 4. To be able to focus more
power to increase the distance, a higher gain is required. To
achieve that, a 2x1 microstrip patch antenna array was designed
for better gain and bandwidth. However, the size of the antenna
is doubled.
Fig. 4. Reflection coefficient versus frequency for a single microstrip patch
antenna
TABLE I
SINGLE MICROSTRIP PATCH ANTENNA PARAMETERS
Parameter Value
Frequency 2.45 GHz
Dielectric constant εr 2.2
Thickness 1.5875 mm
Width of substrate 75 mm
Length of substrate 64.9 mm
Width of patch 65.5 mm
Length of patch 39.1 mm
Width of feed line 4.88 mm
Notch width 0.28 mm
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The 2x1 microstrip patch antenna was designed using a
standard microwave T-junction power divider technique, as
shown in Fig. 5, where the feed line splits into two other feed
lines. A 50 Ω feed line splits into two 100 Ω line, and each 100
Ω feed line connects to a 70.7 Ω feed line. This method helps
to match the impedance accordingly. The 2x1 microstrip patch
antenna parameters is shown in Table II.
Fig. 5. 2x1 microstrip patch antenna array geometry
B. Fabrication & testing
The ease of fabricating microstrip patch antenna is one of its
own advantages. After the array was designed and the results
were satisfying, the antennas were fabricated to be tested. A
photograph of the fabricated microstrip patch array antenna is
shown in Fig. 6. The array was fabricated with an RT/Duroid
5880 with a thickness of 1.57 mm using the milling machine at
CSUN. The microstrip patch arrays were tested in the CSUN
anechoic chamber. It was observed that the simulation results
were slightly different compared to the measured results after
fabrication. The measured results showed a reflection
coefficient of -16 dB as shown in Fig. 7. The normalized
radiation pattern is shown in Fig. 8. The measured gain of the
antenna is 10 dBi. The simulated and measured results were
different due to manufacturing tolerance and simplifications
used for the simulated model.
Fig. 6. A photograph of the microstrip patch array antenna
Fig. 7. Reflection coefficient versus frequency for a 2x1 microstrip patch
array antenna
Fig. 8. Normalized radiation pattern of the 2x1 microstrip patch array antenna
III. RECTIFIER CIRCUITS
This section illustrates the comparison of peak rectifier, full
wave rectifier, and voltage doubler in terms of performance.
The diode has enormous impact on the rectifier’s performance
since it is the main source of power loss. To be suitable for this
microwave power transfer project, the diode must have low
turn-on voltage to operate efficiently. As a result, the diode
Avago HSMS-2820 was chosen for each rectifier in this project.
The smoothing capacitor was SMD Multilayer ceramic
capacitor. This model was used due to its High-Q and low
effective series resistance (ESR). Advanced Design System
(ADS) by Agilent Technologies Inc. was used to simulate and
design the circuits. The components were simulated accurately
considering parasitic parameters from manufacturer's data
sheets. The components were simulated taking into
TABLE II MICROSTRIP PATCH ANTENNA ARRAY PARAMETERS
Parameter Value
Frequency 2.45 GHz
Dielectric constant εr 2.2
Thickness 1.5875 mm
Width of substrate 167 mm
Length of substrate 75 mm
Width of patch 76 mm
Length of patch 39.1 mm
Width of feed line 4.88 mm
Notch width 0.28 mm
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consideration the parasitic parameters from manufacturer's data
sheets. The fabricated circuits were designed with Roger
RT/Duroid 5880 substrate (𝜀𝑟= 2.2 and thickness of 0.79 mm).
A. Peak rectifier
In a peak rectifier, the diode is forward biased and current
flows through the load resistor during the positive half cycles.
During the negative half cycles, the diode is reverse biased.
Thus, the rectifier acts as an open circuit and current will not
flow through the load resistor. Therefore, the output will be
only the positive cycles [8]. The circuit diagram is shown in
Fig. 9, and a photograph of the fabricated rectifier is shown in
Fig. 10.
Fig. 9. Peak rectifier circuit diagram
Fig. 10. A photograph of peak rectifier
B. Full-wave rectifier
The classic full wave rectifier circuit is illustrated in Fig. 11.
The main purpose of the full wave rectifier is to convert the AC
signal to DC. As shown in the schematic, it is made of two parts.
The first part consists of 4 Schottky diodes that operate as
follows: during the positive half cycles, the diodes D2 and D3
become forward biased, the current flows through them into the
load resistor. During the negative half cycles, the diodes D1 and
D4 become forward biased and the current flows through them
into the resistor. The second part of the schematic is the
smoothing capacitor. To reduce the ripple voltage of the output,
a smoothing capacitor is connected in parallel with the load
resistor. The capacitor reduces the ripple by storing and
discharging energy in between the cycles which will result in
smoother DC output. A photograph of the fabricated rectifier is
shown in Fig. 12.
Fig. 11. Full-wave rectifier circuit diagram
Fig. 12. A photograph of full-wave rectifier
C. Voltage Doubler rectifier
The functionality of the voltage doubler rectifier is to double
the input voltage, so the output voltage would be twice the peak
input voltage and it can be represented as Vout= 2(VPeak-VDiode).
It consists of two capacitors and two Schottky diodes, as shown
in Fig. 13. The voltage doubler rectifier can be constructed of
two circuits which are the clamper and rectifier circuits [4]. The
clamper circuit appears during the negative cycles when the
diode D1 is forward biased. The rectifier circuit appears during
the positive cycles when the diode D2 is forward biased. C1 and
D1 rectify the signal during the negative cycles, whereas C2 and
D2 rectify the signal during the positive cycles. However, the
voltage that can be stored on C1 during the negative cycles is
transferred to C2 during the positive cycles. As a result, the
voltage on C2 can be twice VPeak minus 2VDiode [5]. Fig. 14
shows the fabricated voltage doubler rectifier.
Fig. 13. Voltage doubler rectifier circuit diagram
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Fig. 14. A photograph of voltage doubler rectifier
D. Results of rectifier circuits
The three rectifiers were simulated and measured at 2.45
GHz at different load resistances and power inputs. Different
load resistances were used to simulate the output voltage at a
fixed power input of 7.2 dBm for the three rectifiers. As shown
in Fig. 15, the voltage doubler rectifier had the best results.
Furthermore, the rectifiers had similar results for input power
less than 4 dBm, as shown in Fig. 16. However, the voltage
doubler rectifier has better results for input power greater than
4 dBm. Thus, the voltage doubler was selected for the
microwave power transfer system.
Fig. 15. Simulated load resistance versus output voltage at 7.2 dBm for the
three rectifiers
Fig. 16. Measured input power versus output voltage for the three rectifiers
with a 1.1 kΩ load.
IV. OVERALL SYSTEM PERFORMANCE
A. System Simulator Application
To help simulating the system and predicting its
performance, a system simulator application was built using
MATLAB. The application takes several inputs and provide the
power received at the receiver antenna as an output. The inputs
to the application are input power, transmitting antenna gain,
receiving antenna gain, distance between the two antennas,
operating frequency, and polarization angle. Then, for the
second stage of the application, it calculates the DC output
voltage depending on the rectifier type. The system simulator
application graphical user interface is shown in Fig. 17 below.
The application uses the Friis transmission equation to calculate
the received power output which considers two antennas in free
space with no obstruction nearby [9]. The equation is as
follows:
PR =PTGTGRc
2
(4πR𝑓)2
Where: PT is the input power at the transmitter antenna.
GT is the transmitter antenna gain.
GR is the receiver antenna gain.
R is the distance between the two antennas.
𝑓 is the operating frequency.
c is speed of light constant.
Fig.17. System Simulator Application GUI
The application also indicates whether the user is in safe area
according to FCC regulations by calculating the power density.
The maximum power density allowed for general population
according to FCC regulations is 1 mW/cm2 at the operating
frequency of this project [6]. The power density is calculated
with the following equation:
S =PG
4πR2
Where: S is the power density.
P is the input power at the transmitting antenna.
G is the gain of the antennas.
R is the distance to center of radiation of antenna.
B. Overall system results
In this section, the voltage doubler rectifier was used along
with the two antennas to measure the overall system
performance. As shown in Fig. 18, the system consists of a
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signal generator that is connected to the transmitting antenna.
Then the receiver antenna receives the transmitted microwave
signal and passes it to the rectifier which converts it into DC
power to light up the LED.
Fig. 18. A photograph of the microwave wireless power transmission system
The overall system results were measured in two different
setups. For the first set-up, the output voltage was measured for
a fixed signal generator power of 23 dBm and varying distance
between the two antennas with no load resistance. For this
measurement, the two antennas must directly face each other to
maximize the power delivered to the receiving antenna. Any
slight rotation of the antenna will result in power loss. As shown
in Fig. 19, the output voltage reaches above 5 V for short
distances and decreases with longer distances as expected. In
fact, a 1 V output was obtained up to a distance of
approximately 70 cm. For the second set-up, the distance
between the two antennas was fixed to 30 cm and the output
voltage was measured for varying input power. Fig. 20 shows
how the output voltage increases with higher input power. In
this setup, an LED was used to illustrate the results visually.
The maximum distance for which the system could illuminate
an LED was 40 cm at an input power of 23 dBm.
Fig. 19. Measured distance versus output voltage at a fixed signal generator power of 23 dBm
Fig. 20. Measured input power versus output voltage at fixed distance of 30
cm
V. CONCLUSION
A far-field power transmission system was built and tested
successfully as intended. The antennas were designed and
fabricated to achieve the purpose of transmitting power
wirelessly. Afterwards, the three rectifier circuits were built and
tested for better performance in terms of converting microwave
signal to DC power. The overall system succeeded in powering
up an LED wirelessly over a distance of up to 40 cm. However,
achieving high DC levels while staying in the safe
electromagnetic limits was challenging especially when
transmitting power in longer distances due to the FCC
limitations.
Far-field wireless power transmission may be widely relied
on to transmit power wirelessly in the future. Microwave power
transmission can be used in many different applications such as
charging smart phones and other handheld devices. Technology
leaders can enhance the antennas by decreasing its size and
increasing its efficiency. In addition, companies can improve
the efficiency of the rectifiers to get a better overall result. Such
an application may be developed and seen in a market product
in the following years.
REFERENCES
[1] D. M. Pozar, “A Review of Aperture Coupled Microstrip Antennas:
History, Operation, Development, and Applications,” University of
Massachusetts, Amherst, MA, rep., 1996. [2] V. Mohan Kumar, N. Sujith, and S. K. Behera, “Enhancementof
Bandwidthand Gainof a Rectangular Microstrip Patch Antenna,” A thesis
submitted in partial fulfillment of the requirements for the degree of Bachelor of Technology in Electronics and Communication Engineering,
pp. 1–53, 2010.
[3] M. P. Civerolo, “Aperture Coupled Microstrip Antenna Design and Analysis,” In Partial Fulfillment of the Requirements for the Degree
Master of Science in Electrical Engineering, pp. 1–118, Jun. 2010.
[4] A. Sedra and K. Smith, Microelectronic circuits, 6th ed. New York: Oxford University Press, 2009, p. 212.
[5] D. Harrist, "Wireless Battery Charging System Using Radio Frequency
Energy Harvesting", Submitted to the Graduate Faculty of The School of Engineering in partial fulfillment of the requirements for the degree of
Master of Science, p. 13, 2011.
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[6] “RF Safety FAQ,” Federal Communications Commission, 11-Oct-2016. [Online]. Available: https://www.fcc.gov/engineering-
technology/electromagnetic-compatibility-division/radio-frequency-
safety/faq/rf-safety. [7] eCFR - Code of Federal Regulations. [Online]. Available:
https://www.ecfr.gov/cgi-bin/text-
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[9] P. Bevelacqua, “The Friis Equation,” Friis Equation - (aka Friis
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