lin basics 0404 - University of South Florida
Transcript of lin basics 0404 - University of South Florida
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LINEARIZATION:LINEARIZATION:
BY: DR. ALLEN KATZ, MAY 2004 04.16.04
REDUCING DISTORTION IN POWER AMPLIFIERS
• WHY LINEARIZE• TYPES OF LINEARIZERS• THEORY/IDEAL LIMITER• PREDISTORTION LINEARIZERS• PERFORMANCE EVALUATION• RESULTS• CONCLUSIONS
OUTLINE
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IN PAST MOST AMPS USED FOR SC FM MOD SIGNALS
- NL PRODUCTS ELIMINATED WITH LP FILTER-OPERATER AT SATURATION (MAX PWR & EFF)
INPUT
MUX
CHANNEL AMP #1
CHANNEL AMP #2
OUTPUT
MUX
TODAY MULTI-CARRIER AND COMPLEX MODULATED SIGNALS COMMON WHEN MORE THAN ONE CARRIER - DISTORTION PRODUCED (IM)
DISTORTION PRODUCTS
f1 f2AMPLIFIERf1 f2
TO REDUCE DISTORTION TO AN ACCEPTABLE LEVEL
-MUST OPERATE AMPLIFIER AT REDUCED POWER LEVEL(BACKOFF FROM SATURATION)
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Pin 2.5 dB/DIV
TWTA PHASE
TWT POUT
PHASE 5.0 deg/DIV
PHASE
OUT
Ac cos(ωct + M cos[ωmt]) = Ac ΣJn(M) cos([ωc+nωm]t)n= 8
n= - 8
DISTORTION ALSO PRODUCED BY CHANGE IN PHASE WITH POWER LEVEL
FOR A DIGITALLY MODULATED CARRIERDISTORTION PRODUCES SPECTRAL REGROWTH
FREQ 20 MHz/
10 dB/
FREQ 20 MHz/
10 dB/2.5dB OPBO
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SYSTEMATIC PROCEDURE FOR REDUCING DISTORTIONS
USUALLY EXTRA COMPONENTS ADDED TO AN AMPLIFIER
WHEN CONFIGURED IN A SUBASSMBLY OR BOX KNOWNAS A LINEARIZER
THREE COMMON FORMS:1) FEEDFORWARD2) FEEDBACK3) PREDISTORTION
+ TECHNIQUES TO IMPROVE EFFICIENCY USING NL PAs
LINEARIZATION --
CHOICE OF LINEARIZATION
• LEVEL OF LINEARITY (DISTORTION REDUCTION) NEEDED.
• BANDWIDTH REQUIRED (SIGNAL AND OPERATIONAL).
• COST/COMPLEXITY CONSTRAINTS.
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LINEARIZERS HAVE BEEN USED WITH
•FET SSPAs (GaAs, MOS, LDMOS)
•TWTAs and KLYSTRONS
• BIPOLAR SSPAs (CLASS A, AB, B)
AMP LAMP AMP LAMP
AMP LAMP AMP LAMP
“SAME” Distortion
“SAME” Distortion
POWER OUT
Greater Ouput Power
Efficiency
Greater Efficiency
LINEARIZERS ALLOW HPAs TO OPERATE CLOSER TO SAT
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WANT TO OPTIMIZE EFFICIENCY AND SATURATED POWER, NOT LINEARITY
EXCELLENT RESULTS CAN BE OBTAINED WITH CLASS A-B AND B AMPS BOTH FET AND BIPOLAR
YOU CAN’T LINEARIZE AN AMPLIFIERTHAT IS ALREADY LINEAR!
FIRST RULE:
IDEAL AMPLIFIER CHARACTERISTIC
φ
Pout
inP
WANT CONSTANT GAIN AND PHASE
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SATELLITE --•IMD PRODUCTS ADD TO THERMAL NOISE IF C/I = CNR THEN CNR DEGRADES BY 3 dB
•WANT C/I > CNR + 10 dB FOR NEGLIGIBLE DEG. (< .5 dB)IF CNR = 16 dB THEN C/I = 26 dB
•IF C/I = CNR + 6 THEN CNR = CNR DEG. BY 1 dB
CELLULAR --•INTERFERENCE FROM TX TO ADJACENT RX A PROBLEM --CAN NEED C/I > 35 ~ 70 dB.
•FOR DIGITAL MOD, 16QAM … 8PSK NEED HIGH C/I TO KEEP BER DOWN.
IMPROVEMENT DEPENDS ON ACCEPTABLE DIST LEVEL
FEEDFORWARD
•RELATIVELY COMPLEX
•NOT WORKABLE AS STAND-ALONE UNIT
•NOT EFFECTIVE FOR OPBOs < 6 dB
•MOST USEFUL FOR VERY HIGH LINEARITY APPLICATIONS
Sin Sout 1 Sout 2
MAIN AMP
AUX AMP Scor
IMD
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MINIMUM FEEDFORWARD OPBO FOR IMD CANCELATION (20 dB)
1) AUX AMP SIZE, 2) OUTPUT COUPLER COEF.
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8
7
6
5
4
3
2
1
00 1 2 3 4 5 6 7 8 9 10
Aux Amp Size Relative to Main Amp in dB
Min
. OPB
O fo
r IM
D C
ance
llatio
n in
dB K2 3 dB
K2 10 dBK2 6dB
DEPENDS ON: 1) AUX AMP SIZE, 2) OUTPUT COUPLER COEF.
FEEDBACK LINEARIZATION
*FEEDBACK (NETWORK)NET-
WORK
AMP
- NARROW BAND- STABILITY PROB- REDUCED GAIN- DIFF TO ADJ
*INDIRECT FEEDBACK
-OPERATES ON ENVELOPE-VERY LIMITED BW < 1/(4∆tS)-CAN BE POLAR OR CARTESIAN
AMP
+
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CARTESIAN FEEDBACK ELIMINATES THE NEED FOR PHASE CORRECTION CIRCUITRY
•RELATIVELY SIMPLE CIRCUITRY
PREDISTORTION
•WIDE BAND (>20% BW)
•MOST POPULAR FOR MICRO/MILLIMETER WAVE
•EASILY IMPLEMENTED AS A STAND-ALONE UNIT
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LINEARIZER GAIN DEPENDS ON INPUT TO HPA
• THE GAIN OF THE LINEARIZER (GL) MUST INCREASE BY THE SAME AMOUNT THE HPA’s GAIN (GA) DECREASES.
• GL(PoutL) - GLss = - [GA(PinA) - GAss] PoutL = PinA
• ΦL(PoutL) - ΦLss = - [ΦA(PinA) - ΦAss] PoutL = PinA
• GL(PinL) = GLss+ GAss - GA(PinL + GL(PinL))
• ΦL(PinL) = ΦLss+ ΦAss - ΦA(PinL + GL(PinL))
• ΦL DEPENDS ON THE GL AND CANNOT BE SET IDENPENDENTLY
0-20 -18 -16 -14 -12 -10 -8 -6 -4 -2 0
10
15
20
5
PIN dB
25
30
35
40
LIN PHASE
LIN GAIN
PHA
SE IN
DEG
REE
S
45
-4.5
-3.5
-3.0
-2.5
-4.0
-2.0
-1.5
-1.0
-0.5
0
GAI
N IN
dB
AN IDEAL LINEARIZER MUST PROVIDE A GAIN EXPANSION THAT APPROACHES INFINITY NEAR SATURATION
dG/dP =>∞ as Pin => Sat
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FORMS OF PREDISTORTION LINEARIZERS
Vout (HIGH)
Vin
Vout (LOW)
Vnl
1. TRANSMISSIONLIN
NL
F
2. REFLECTIVE
NL
F
3. IN LINE
TECHNIQUES TO IMPROVE EFFICIENCY USING NL PAs
• MANY WAYS TO ACCOMPLISH.
• CLASSICAL “KHAN METHOD” DEMODS ENVELOPE AND LIMITS SIGNAL. THEN REMODULATES AT OUTPUT PA.
• LINC SYSTEMS USE OBTAIN LINEAR AMPLIFICATION BY COMBINING TWO NON-LINEAR PAs.
• LOAD MODULATION AND OUTPHASING (DOHERTY – ONE EXAMPLE)
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EER – ENVELOPE ELIMINATION AND RESTORATION
IF ELIMINATE ENVELOPE, SIGNAL CAN BE AMPLIFIED IN NL PA OPERATED AT OR NEAR SATURATION.
LINC – LINEAR AMPLIFICATION WITH NON-LINEAR COMPONENTS
CAN OBTAIN ANY AMPLITUDE FROM THE SUM OF 2CONSTANT AMPLITUDE SIGNALS OF VARIABLE PHASE
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DIGITAL PREDISTORTION
• CAN PRODUCE CURVES OF ANY SHAPE• NORMALLY PROCESS AT BASEBAND• CAN USE EITHER G AND Φ OR I AND Q• MUST SAMPLE AT > 2 X CORRECTION BW FOR G AND Φ• BUT ONLY > CORRECTION BW FOR I AND Q• CORRECTION BW (CBW) ≥ 3 x BW OF SIGNAL• MUST USE MANY BITS FOR HIGH CANCELATION (<6 dB/)
MIX DOWN TO BB MIX UP TO IFIF RF
BW
0 3 ω0 6ω0
A/DSIGNAL
INTERPOLATE
II~
cos 3 ω0t(1, 0, -1, 0)
Q~
sin 3ω0t(1, 0, -1, 0)
CALCULATE
cos 3 ω0t
sin 3ω0tIY+QX
D/A FIL
IX-QY
smoothing
HPA
ω1+3ω0
~ ω1
R
X (R)LUT
Y (R)LUT
Q
COMPUTE
UPDATED
VALUES
FOR
X(R), Y(R)
UPDATEX(R), Y(R)
R'
INTERPOLATE
A/D
I~
Q~
cos 3 ω0t
sin 3ω0t
LUT = Look Up Table
T= sampling period
3w0 (4∆T) = 2 π3f0 (4∆T) = 1
fs = 1/ ∆T
fs = 12 f 0 = 6BW
SPECTRUM
DIGITAL ADAPTIVE PREDISTORTION
ADAPTIVE SYSTEMS CORRECT AT << ENVELOPE RATE
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• ADVANTAGES:* ACCURATE CORRECTION OVER WIDE DYNAMIC
RANGE AND FOR IRREGULAR NON MONOTONIC CHARACTERISTICS
* EASY TO MODIFY AND UPDATE * SIMPLE TO IMPLEMENT AS ADAPTIVE SYSTEM
• DISADVANTAGES:* CORRECTION BANDWIDTH LIMITED BY
SAMPLING RATE: SR = CBW = N X BW* COST CAN BE HIGHER THAN ANALOG * POWER CONSUMPTION CAN BE HIGH* WIDE BW SYSTEMS DIFFICULT TO IMPLEMENT
DIGITAL PREDISTORTION
PERFORMANCE EVALUATION
MAGNITUDE & PHASE IMPORTANT INDICATORS OF PERFORMANCE
Pin 2.5 dB/DIV
TWTA PHASE
LTWTA PHASE
TWT POUT
LTWTA POUT
PHASE 5.0 deg/DIV
Pin 2.5 dB/DIV
LTWTA GAIN
TWTA GAIN
LTWTA POUT
TWTA POUT
GAIN 0.5 dB/DIV Pout 2.5 dB/DIV
Pin 2.5 dB/DIV
TWTA PHASE
LTWTA PHASE
TWT POUT
LTWTA POUT
PHASE 5.0 deg/DIV
** OBTAIN WITH POWER SWEEP
SEPARATION OF 1 dB COMPRESSION AND SATURATIONPROVIDES GAGE FOR COMPARISON
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C/I (CARRIER TO IMD) MEASUREMENT
• MANY DIFFERENT STANDARDS MAKE COMPARISON DIF.
• DATA USUALLY PRESENTED REL TO BACKOFF FROM SAT.
• SAT POINT SHOULD BE SINGLE CARRIER SAT.2 CARRIER SAT ABT 1 dB LOWER, NOISE ABT 1.5 dB.
• CAN NOT USE COMPRESSION POINT FOR REFERENCE.1 dB = SAT - D
• BOTH IPBO AND OPBO USED … IPBO CAN BE MISLEADING.BEST TO REFER TO OPBO- OUTPUT LEVEL IS WHAT’S IMPORTANT!
OFTEN RESULTS PRESENTED FOR C/I3 ONLY
7 73 3
5th 5th
th thrd rd
With Linearizers, not uncommon for 5th order terms to be greater than 3rds or of same order
Total C/I preferred to C/I3
C/Imin is a good compromise
C/I total = C/ Ι3 2 + Ι5 2 + Ι7 2 + ...Σ
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IMD TERMS CAN BE NON-SYMMETRICAL
UPPER & LOW ODD ORDER AM/AM TERMS IN PHASE
UPPER & LOW ODD ORDER AM/PM TERMS OUT OF PHASE
DUE TO MEMORY EFFECTS (AM/AM AND AM/PM)
A LINEARIZER IMPROVES LINEARITY OF A CLASS A SSPA
Rel
ativ
e Po
wer
Out
put 0
.5 d B/D
IV
START -10.0 dBm CW 1.9500 GHz STOP 15.0 dBm
Gai
nG
hang
e0 .5
dB
/DIV
SAT
AMPL/AMP
GAIN
PHASE
AMPSAT
AMP
L/AMP
L/AMP
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70
65
60
55
50
45
40
35
30
25
20
15
10
1 2 3 4 5 6 7 8 9 10 11 12 13 14 15
OUTPUT BACKOFF IN dB
C/I
IN d
B L/SSPA
SSPA
LINEARIZATION OF A CLASS A SSPA PROVIDES ONLY
A 0.5 dB POWER INCREASE FOR A C/I OF 26 dB,BUT A 2.5 dB POWER INCREASE FOR A C/I OF 50 dB
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40
35
30
25
20
15
101 2 3 4 5 6 7 8 9 10
C/I (MIN) IN dB
OUTPUT POWER BACKOFF IN dB
L/SSPA
SSPA26 dB
LINEARIZATION OF LESS LINEAR CLASS AB SSPA
PROVIDES > 1.5 dB POWER INCREASE FOR C/I OF 26 dB.
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WITH A TWTA A C/I = 26 dB CAN OBTAIN > 3 dB POWER INCREASE
WITH MULTIPLE CARRIERS THE IMPROVEMENT IS EVEN GREATER!
1 2 3 4 5 6 7 8 9 1010
15
20
25
30
35C
/I in
dB
OUTPUT POWER BACKOFF IN dB
40
45
>3dB
LTWTA
TWTA
High Band
Mid Band
Low Band
6dB
MULTIPLE CARRIERS (N>2)
• NO SIMPLE RELATIONSHIP BETWEEN C/I FOR 2 AND N CARRIER CASE
• EXERCISE OVER RANGE Ppk = 2NPav
14 16 18 20 22 24 26 28 30 32
1
2
3
4
5
6
0OPB
O R
EUC
TIO
N I N
dB
C/I IN dB
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OPBO IMPROVEMENT
2-TONE
4-TONENPR
• GREATER IMPROVEMENT(REDUCTION IN OPBO) FOR A GIVEN C/I AS N INCREASES
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NPR - NOISE POWER RATIO
NoisePedestal
Notch
Noise BPF Notch
MEASURE OF N-CARRIER C/I
WANT DEPTH OF GENERATOR NOTCH > 10 dB BELOW NPR OF INTEREST
NPR PREDICTS AMPLIFIER PERFORMANCEWITH MANY CARRIERS
1 2 3 4 5 6 7 8 9 10 11
10
15
20
25
30
35
5
LTWTA
TWTA
C/I
in d
B
OUTPUT POWER BACKOFF IN dB
4 dB
FOR C/I = 25 dB OBTAIN ALMOST 6 dB INCREASE IN POWER.
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NPR OF CLASS AB SSPA
10
15
20
25
30
35
1 2 3 4 5 6 7 8 9 10 11OPBO in dB
NPR
in d
B
PROVIDES SIGNIFICANT REDUCTION IN SPECTRUM
REF LEVEL0.5 dBm
TWT ONLY
4.0 dB B.O.
4.0 dB B.O.WITH LINEARIZER
10 dB/
VBW 1 kHZ
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> 2 dB POWER INCREASE
EVEN NEAR SAT
REDUCTION IN SPECTRAL REGROWTH PROVIDED BY LINEARIZATION OF A TWTA
0 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17
25
30
35
40
45
50
20
Car
rier t
o N
oise
Rat
i o
OPBO IN dB
15dB
LTWTA
TWTA
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01 2 3 4 5 6 7 8 9 10
20
30
40
10
OUTPUT BACKOFF IN dB
50
60
70
80
C/I
IN d
B
IDEAL LINEARIZER PERFORMANCE IS LIMITED BY SIGNAL PEAK-TO-AVERAGE CHARACTERISTICS (PAC)
2-TONE
MANY-TONE (NPR)
PAC SETS MINIMUM BACKOFF OF PA!CANNOT IMPROVE BY LINEARIZATION.
MUST USE PA WITH HIGHER POWER/EFFICIENCY
DSP L/TWTA AT 3 dB OPBO – C/I > 50 dB
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TWO KINDS OF BANDWIDTH1) STATIC BANDWIDTH - ABILITY OF LIN MAG/PHASE TRANSFER RESP TO
EQUALIZE AMP AT ALL FREQ OF INTEREST
2) DYNAMIC BANDWIDTH - ABILITY OF LIN MAG/PHASE TRANSFER RESP TO FOLLOW ENVELOPE OF SIGNALS
- MEAS WITH 2 CLOSE SPACED TONES AT ALL FREQ OF INTEREST
- MEAS WITH 2-TONE SIGNAL IN WHICH THESPACING OF THE TONES IS INCREASED
THE LINEARITY OF AMPLIFIERS DEGRADE WITH INCREASING CARRIER SPACING
C/I5 LOWER
4 dB OPBO
40
35
30
25
20
15
10
1 2 3 4 5 6 7 8 9 10 20 30 40 50 60 70 80 90 100CARRIER SPACING (MHz)
C/I
(dB
)
C/I3 UPPER
C/I3 LOWER
C/I5 UPPER
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MAJOR CAUSE OF DEGRADATION --
ENVELOPE FREQUENCY Fe = F∆/2
TRANSFER CHARACTERISTICS CHANGE WITH Fe
INABILITY OF AMPLIFIERS TO FOLLOW RAPIDLY CHANGING ENVELOPE
MEMORY EFFECTSMEMORY EFFECTS
• Memory Effects are changes in a Power Amplifier’s (PA) non-linear characteristics resulting from the past history of the input signal.
Vo = f(Vin, time)
• Primary cause drain/collector and gate/base bias change.
• Thermal, device and frequency are also factors.
• Standard predistortion linearizers depend on a stable non-linear response, and can be particularly degraded by memory effects.
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IMPROVEMENT IN C/I RESULTING FROM ADDED LOWINDUCTANCE DRAIN CAPACITORS (RESONATE AT 12 MHz)
40
35
30
25
20
15
10
Linearizer with CapsLinearizer without CapsNo Linearizer with CapsNo Linearizer without CapsLinearized (1MHz Average)Non-Linearized (1 MHz Average)
C/I
IN d
B
OUTPUT BACKOFF IN dB
30 MHz CARRIER SPACING
LINEARIZERS INCREASE HPA POWER CAPACITY AND EFFICIENCY FOR MULTI-CARRIER AND COMPLEX DIGITAL SIGNALS
NEW LINEARIZER DESIGNS HAVE GREATLY ENHANCED PERFORMANCE
SSPAs - BENEFIT GREATEST FOR CLASS B AND AB 2 X POWER INCREASE IN HIGH LIN APPLICATIONS
TWTAS - 4 X POWER INCREASE AND DOUBLE EFFICIENCY
SUMMARY
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PREDISTORTION:
ADVANTAGES SIMPLICITY, WIDEBAND, VIABLE BOTH LOW AND HIGH LIN. DSP CAN PROVIDE VERY HIGH LIN.
INDIRECT FEEDBACK:
WORKS WELL, BUT LIMITED IN BANDWIDTH.
FEEDFORWARD:
LINEARIZATION IS MOST VALUABLEWHEN VERY HIGH LIN REQUIRED.
SUMMARY
FOR MORE INFORMATION
1. A. Katz, “Linearization: Reducing Distortion in Power Amplifiers,” IEEE Microwave Magazine, pp. 37-49, December 2001.
2. Vuolevi and Rahkonen, “Distortion in RF Power Amplifiers”, Artech House, 2003.
3. S. Cripps, “Advanced Techniques in RF Power Amplifier Design”, Artech House, 2002.
4. A. Katz and R. Gray, “The Linearized Microwave Power Module,” MTT-S International Microwave Symposium Digest, June, 2003.
5. A. Katz, “Performance Of Multi-carrier 16QAM Over a Linearized TWTA Satellite Channel,” AIAA 20th International Communications Satellite Systems Conference Proceedings, Montreal, May 2002.
6. P. Kenington, “Methods Linearize RF Transmitters and Power Amps, Part 1, ”Microwaves & RF Magazine,” pp. 103-116, December 1998, Part 2, pp. 79-89, January 1999.