Lecture 5 Transmission Line Impedance Matching
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Transcript of Lecture 5 Transmission Line Impedance Matching
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8/2/2019 Lecture 5 Transmission Line Impedance Matching
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EECS 117
Lecture 5: Transmission Line Impedance Matching
Prof. Niknejad
University of California, Berkeley
University of California, Berkeley EECS 117 Lecture 5 p. 1/
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Open Line I/V
The open transmission line has infinite VSWR andL = 1. At any given point along the transmission line
v(z) = V+
(ejz + ejz) = 2V+
cos(z)
whereas the current is given by
i(z) = V+
Z0(ejz ejz)
or
i(z) = 2jV+Z0
sin(z)
University of California, Berkeley EECS 117 Lecture 5 p. 2/
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Open Line Impedance (I)
The impedance at any point along the line takes on asimple form
Zin() = v()i() = jZ0 cot()
This is a special case of the more general transmission
line equation with ZL = .Note that the impedance is purely imaginary since anopen lossless transmission line cannot dissipate any
power.
We have learned, though, that the line stores reactiveenergy in a distributed fashion.
University of California, Berkeley EECS 117 Lecture 5 p. 3/
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Open Line Impedance (II)
A plot of the input impedance as a function of z isshown below
-1 -0.8 -0.6 -0.4 -0.2 0
2
4
6
8
10
Zin(/4)
Zin(/2)
z
Zin(z)
Z0
The cotangent function takes on zero values when approaches /2 modulo 2
University of California, Berkeley EECS 117 Lecture 5 p. 4/
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Open Line Impedance (III)
Open transmission line can have zero input impedance!
This is particularly surprising since the open load is ineffect transformed from an open
A plot of the voltage/current as a function of z is shownbelow
-1 -0.8 -0.6 -0.4 -0.2 00
0. 5
1
1. 5
2
v(z) i(z)Z0
z/
v/v+
v(/4)
i(
/4)
University of California, Berkeley EECS 117 Lecture 5 p. 5/
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Open Line Reactance
/4 capacitor < /4 capacitivereactance
= /4 short (actslike resonant seriesLC circuit)
> /4 but < /2 inductive reactance
And the process re-peats ...
.25 .5 .75 1.0 1.25
-7.5
-5
-2.5
0
2. 5
5
7. 5
10
jX(z)
z
University of California, Berkeley EECS 117 Lecture 5 p. 6/
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/2 Transmission Line
Plug into the general T-line equation for any multiple of/2
Zin(m/2) = Z0ZL +jZ0 tan(
/2)
Z0 +jZL tan(/2)m/2 = 2
m2
= m
tan m = 0 if m ZZin(m/2) = Z0ZLZ0 = ZLImpedance does not change ... its periodic about /2
(not )
University of California, Berkeley EECS 117 Lecture 5 p. 7/
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/4 Transmission Line
Plug into the general T-line equation for any multiple of/4
m/4 =
2
m
4 =
2mtan m
2= if m is an odd integer
Zin(
m/4) = Z
2
0
ZL
/4 line transforms or inverts the impedance of theload
University of California, Berkeley EECS 117 Lecture 5 p. 8/
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Effect of Source Impedance
Zs
Vs ZLZ0
Up to now we have considered only a terminatedsemi-infinite line (or matched source)
Consider the effect of the source impedance Zs
The voltage at the input of the line is given by
vin = v() = v+ej(1 + Le2j)
University of California, Berkeley EECS 117 Lecture 5 p. 9/
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Effect of Source Impedance
By voltage division, the voltage can also be expressedas
vin =Zin
Zin + ZsVs
Equating the two forms we arrive at
v+ = ZinVs(Zin + Zs)ej(1 + Le2j)
In a matched system, we desire the input impedance
seen into the T-line to be the conjugate of the sourceimpedance (maximum power transfer)
Impedance matching is required to acheive this goal
University of California, Berkeley EECS 117 Lecture 5 p. 10/
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/4 Impedance Match
Rs
Vs RL
/4
Z0 =RLRs
If the source and load are real resistors, then a
quarter-wave line can be used to match the source andload impedances
Recall that the impedance looking into the quarter-wave
line is the inverse of the load impedance
Zin(z = /4) = Z20
ZL
University of California, Berkeley EECS 117 Lecture 5 p. 11/
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SWR on /4 Line
In this case, therefore, we equate this to the desired
source impedance Zin =Z20RL
= Rs
The quarter-wave line should therefore have acharacteristic impedance that is the geometric mean
Z0 =
RsRL
Since Z0 = RL, the line has a non-zero reflectioncoefficientSW R =
RL
RLRs
RL +
RLRs
It also therefore has standing waves on the T-line
The non-unity SWR is given by1+|L|1|L|
University of California, Berkeley EECS 117 Lecture 5 p. 12/
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Interpretation of SWR on /4 Line
Consider a generic lossless transformer (RL > Rs)
Thus to make the load look smaller to match to thesource, the voltage of the source should be increased inmagnitude
But since the transformer is lossless, the current willlikewise decrease in magnitude by the same factor
With the /4 transformer, the location of the voltageminimum to maximum is /4 from load (since the load isreal)
Voltage/current is thus increased/decreased by a factorof 1 + |L| at the loadHence the impedance decreased by a factor of
(1 + |L|)2University of California, Berkeley EECS 117 Lecture 5 p. 13/
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Matching with Lumped Elements (I)
Rs
Vs RLZ0
1
Y = Y0 jB
jB
Y = Y0
Recall the input impedance looking into a T-line variesperiodically
Zin(
) = Z0ZL +jZ0 tan()
Z0 +jZL tan()
Move a distance 1 away from the load such that thereal part of Zin has the desired value
University of California, Berkeley EECS 117 Lecture 5 p. 14/
M hi i h L d El (II)
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Matching with Lumped Elements (II)
Then place a shunt or series impedance on the T-line toobtain desired reactive part of the input impedance (e.g.zero reactance for a real match)
For instance, for a shunt match, the input admittancelooking into the line is
y(z) = Y(z)/Y0 = 1 Lej2z
1 + Lej2z
At a distance 1 we desire the normalized admittance to
be y1 = 1jbSubstitute L = e
j and solve for 1 and let = 2z +
1 ej
1 + ej= 1
2
j2 sin 1 + 2 cos + 2
University of California, Berkeley EECS 117 Lecture 5 p. 15/
M hi i h L d El (III)
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Matching with Lumped Elements (III)
Solve for (and then 1) from (y) = 1
= 2 = cos1()
1 =
2=
4
cos1()
At 1, the imaginary part of the input admittance is
b = (y1) = 2
12
Placing a reactance of value b in shunt providedimpedance match at this particular frequency
If the location of 1 is not convenient, we can achievethe same result by move back a multiple of /2
University of California, Berkeley EECS 117 Lecture 5 p. 16/
M t hi ith St b (I)
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Matching with Stubs (I)
Rs
Vs RLZ0
1
Y = Y0 jB
Y = Y0
jB
At high frequencies the matching technique discussedabove is difficult due to the lack of lumped passive
elements (inductors and capacitors)
But short/open pieces of transmission lines simulatefixed reactance over a narrow band
A shorted stub with < /4 looks like an inductorUniversity of California, Berkeley EECS 117 Lecture 5 p. 17/
M t hi ith St b (II)
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Matching with Stubs (II)
Rs
Vs RLZ0
1
Y = Y0 jB
Y = Y0
jB
open stub
An open stub with < /4 looks like a capacitor
The procedure is identical to the case with lumpedelements but instead of using a capacitor or inductor,we use shorted or open transmission lines
Shunt stubs are easier to fabricate than series stubs
University of California, Berkeley EECS 117 Lecture 5 p. 18/
L T i i Li
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Lossy Transmission Lines
Lossy lines are analyzed in the same way as losslesslines
Low-loss lines are often approximated as lossless lines
Recall the general voltage and current on the line
v(z) = v+
ez
+ v
ez
i(z) =
v+
Z0 ez
v
Z0 ez
Where = + j is the complex propagation constant.On an infinite line, represents an exponential decay in
the wave amplitude
v(z) = ez
v+ejz
University of California, Berkeley EECS 117 Lecture 5 p. 19/
T i i Li Di i
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Transmission Line Dispersion
What about dispersion? Is the amplitude attenuation afunction of frequency? If so, the wave will distort.Moreover, how does the speed of propagation vary with
frequency?For a dispersionless line, the output should be a linearlyscaled delayed version of the input vout(t) = Kvin(t ),or in the frequency domain
Vout(j) = KVin(j)ej
The transfer function has constant magnitude |H(j)|and linear phase H(j) = The propagation constant j should therefore be a
linear function of frequency and should be a constantIn general, a lossy transmission line has dispersion
University of California, Berkeley EECS 117 Lecture 5 p. 20/