Current Programmed Control (i.e. Peak Current-Mode Control...
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ECEN5807
Current Programmed Control(i.e. Peak Current-Mode Control)
More Accurate Models
ECEN 5807Lecture 25
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More Accurate CPM Models: Outline
Sampled-data modeling of inductor dynamics in current programmed mode
• Instability of the current loop and the need for compensation (“artificial”) ramp (Textbook Section 12.1)
• Improved modeling of high-frequency dynamics to enable design of wide-bandwidth voltage loops
More accurate averaged model• Large-signal and small-signal averaged modulator model• Accurate averaged small-signal models, including high-
frequency dynamics• Accurate modeling of line-to-output responses
Discussion of results for basic convertersCPM model for simulationsDesign examples
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High-frequency small-signal inductor-current dynamics
Assume that voltage perturbations are negligibly small at high frequencies: the slopes m1 and m2 can be considered constant
Apply sampled-data modeling:
)(ˆ][ˆ][ˆˆ)(ˆ * tininiiti LLccc
)(ˆ)(ˆ)(ˆ)(ˆ1)(ˆ sizizijksiT
si LLck
scs
c
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Discrete-time dynamics ][ˆ][ˆ nini Lc
sLL Tndmmnini ][ˆ)(]1[ˆ][ˆ21
sLc Tndmnini ][ˆ]1[ˆ][ˆ1
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Discrete-time dynamics ][ˆ][ˆ nini Lc
sLL Tndmmnini ][ˆ)(]1[ˆ][ˆ21
sLc Tndmnini ][ˆ]1[ˆ][ˆ1
][ˆ)1(]1[ˆ ][ˆ]1[ˆ][ˆ1
21
1
2 nininim
mmnimmni cLcLL
'
1
2
1
2
DD
MM
mm
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Instability for D > 0.5
][ˆ)1(]1[ˆ ][ˆ ninini cLL
'
1
2
1
2
DD
MM
mm
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Small-signal perturbation with compensation ramp
ic[n]
m1(t) m2(t)
ic + ic
iL[n]
d[n]TsiL[n-1]
ma(t)
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Discrete-time dynamics with compensation ramp: ][ˆ][ˆ nini Lc
sLL Tndmmnini ][ˆ)(]1[ˆ][ˆ21
saLc Tndmmnini ][ˆ)(]1[ˆ][ˆ1
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sLL Tndmmnini ][ˆ)(]1[ˆ][ˆ21
][ˆ)1(]1[ˆ ][ˆ]1[ˆ][ˆ1
21
1
2 nininimmmmni
mmmmni cLc
aL
a
aL
2
2
1
2
'
1
mm
DD
mm
mmmm
a
a
a
a
Discrete-time dynamics with compensation ramp: ][ˆ][ˆ nini Lc
saLc Tndmmnini ][ˆ)(]1[ˆ][ˆ1
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][ˆ)1(]1[ˆ ][ˆ ninini cLL
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][ˆ)1(]1[ˆ ][ˆ ninini cLL
Discrete-time dynamics: )(ˆ)(ˆ zizi Lc
Z-transform: )(ˆ)1()(ˆ )(ˆ 1 zizzizi cLL
1 11
)(ˆ)(ˆ
zzi
zi
c
L
Discrete-time (z-domain) control-
to-inductor current transfer function:
ss TjsT ee
11
11
Difference equation:
• Pole at z = • Stability condition: pole inside the unit circle, || < 1
• Frequency response (note that z1 corresponds to a delay of Ts in time domain):
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Equivalent hold:
ic[n]
m1(t) m2(t)
ic + ic
iL[n]
d[n]TsiL[n-1]
ma(t)
)(ˆ)(ˆ ),(ˆ][ˆ sizitini LLLL
iL(t) iL[n]
Ts
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Equivalent hold
The response from the samples iL[n] of the inductor current to the inductor current perturbation iL(t) is a pulse of amplitude iL[n] and length Ts
Hence, in frequency domain, the equivalent hold has the transfer function previously derived for the zero-order hold:
se ssT1
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Complete sampled-data “transfer function”
s
sT
sTc
L
sTe
esisi s
s
1
11
)(ˆ)(ˆ
2
2
1
2
'
1
mm
DD
mm
mmmm
a
a
a
a
Control-to-inductor current small-signal response:
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Example
CPM buck converter:Vg = 10V, L = 5 H, C = 75 F, D = 0.5, V = 5 V, I = 20 A, R = V/I = 0.25 , fs = 100 kHz
Inductor current slopes:m1 = (Vg – V)/L = 1 A/sm2 = V/L = 1 A/s
2
2
2
2
1
2
1
1
'
1
mmmm
mm
DD
mm
mmmm
a
a
a
a
a
a
D = 0.5: CPM controller is stable for any compensation ramp, ma/m2 > 0
s
sT
sTc
L
sTe
esisi s
s
1
11
)(ˆ)(ˆ
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Control-to-inductor current responses for several compensation ramps (ma/m2 is a parameter)
102
103
104
105
-40
-30
-20
-10
0
10
20
mag
nitu
de [
db]
iL/ic magnitude and phase responses
102
103
104
105
-150
-100
-50
0
frequency [Hz]
phas
e [d
eg]
ma/m2 = 0.1
ma/m2 = 0.5ma/m2= 1
ma/m2 = 5
5
10.5
0.1
MATLAB file: CPMfr.m
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First-order approximation
hfs
s
sT
sTc
L
sssTe
esisi s
s
1
1
)/(111
11 1
1)(ˆ)(ˆ
)/(1
)/(1
s
ssT
s
s
e s
s
a
shf
f
mmDD
ff
2
221
111
Control-to-inductor current response behaves approximately as a single-pole transfer function with a high-frequency pole at
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Control-to-inductor current responses for several compensation ramps (ma/m2 = 0.1, 0.5, 1, 5)
102
103
104
105
-40
-30
-20
-10
0
10
20
mag
nitu
de [
db]
iL/ic magnitude and phase responses
102
103
104
105
-150
-100
-50
0
frequency [Hz]
phas
e [d
eg]
1st-order transfer-function approximation
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Second-order approximation
2
2/)2/(11
21
11 1
1)(ˆ)(ˆ
ss
s
sT
sTc
L
sssTe
esisi s
s
2
2
2/)2/(21
2/)2/(21
ss
sssT
ss
ss
e s
2
221
12112
mmDD
Qa
Control-to-inductor current response behaves approximately as a second-order transfer function with corner frequency fs/2 and Q-factor given by
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102
103
104
105
-40
-30
-20
-10
0
10
20m
agni
tude
[db
]iL/ic magnitude and phase responses
102
103
104
105
-150
-100
-50
0
frequency [Hz]
phas
e [d
eg]
Control-to-inductor current responses for several compensation ramps (ma/m2 = 0.1, 0.5, 1, 5)
2nd-order transfer-function approximation
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Conclusions
• In CPM converters, high-frequency inductor dynamics depend strongly on the compensation (“artificial”) ramp slope ma
• Without compensation ramp (ma = 0), CPM controller is unstable for D > 0.5, resulting in period-doubling or other sub-harmonic (or even chaotic) oscillations
• For ma = 0.5m2, CPM controller is stable for all D
• Relatively large compensation ramp (ma > 0.5m2) is a practical choice not just to ensure stability of the CPM controller, but also to reduce sensitivity to noise
• For relatively large values of ma, high-frequency inductor current dynamics can be well approximated by a single high-frequency pole
• Second-order approximation is very accurate for any ma
• Next: more accurate averaged model, including high-frequency dynamics