Characterization of frequency-selective surface spatial filters in a rectangular waveguide

research paper

Characterization of frequency-selectivesurface spatial filters in a rectangularwaveguide

fabien debarros1,2

, pierre lemaitre-auger1

, alysson vasconcelos gomes de menezes1,3

,

romain siragusa1

, tan-phu vuong4

, guy eymin petot tourtollet2

and

glauco fontgalland3

The possibility to characterize infinite and periodic frequency-selective surfaces (FSS) filters that have two orthogonal axes ofsymmetry inside a waveguide is reported. Thus, preliminary measurements can rapidly be obtained at low cost with fewelementary cells instead of using a large FSS panel in free space. This is possible because of the equivalence that existsbetween the electromagnetic fields of two symmetric and oblique plane waves incident on and reflected from an infinite per-iodic surface and the incident/reflected fields that exist inside a single-mode rectangular waveguide containing a finite numberof elementary cells. Comparisons of the measurements with some full-wave simulations for FSS belonging to the first threegroups as they were defined by Munk confirm the good agreement between them. This is an interesting and simple assessmenttool concerning the fabrication quality of FSS. The extension of this technique to non-symmetric FSS patterns is also discussedand supported by experimental and simulation results. The limitations of the technique are finally discussed.

Keywords: Frequency-selective surfaces, FSS, Waveguide

Received 7 June 2011; Revised 14 October 2011; first published online 5 January 2012

I . I N T R O D U C T I O N

Frequency-selective surfaces (FSS) are passive spatial com-ponents usually made of periodic metallic elements placedover a dielectric substrate [1]. They present the interestingproperty of filtering electromagnetic waves (EMW).Depending on the pattern chosen, low-pass, high-pass, band-pass, as well as band-stop filters can be designed. Their polyva-lence and simplicity make them very attractive for several appli-cations, like radomes, dichroıc filters, or artificial magneticconductors. Among them, one application that is gettingmore and more interesting from the scientific community isthe development of an electromagnetic shielding for a safeindoor environment [2–8]. Several reasons explain this. First,with the recent important growth of wireless telecommunica-tion systems, EMW are now present everywhere in our urbanenvironment. Even if it is still a controversial subject, some

studies report on the harmful effects of an overuse of wirelessGlobal System for Mobile Communications (GSM) technology[9]. It is thus natural that a part of the population is seeking forprotection against EMW. A second reason is the need to protectthe data that transit through WiFi networks. All wireless com-munications are a weakness in a secure system [10] and confin-ing the EMW within a secure zone is the only protection whichis 100% safe. A third reason to control EMW comes from thefact that the efficiency of a wireless communication decreaseswhen its surrounding is too densely populated with wirelessnetworks [11]. Physical separation of the networks wouldthus be beneficial.

Whatever the need for an EM shielding is, its practicalrealization on an industrial basis requires a reliable andlow-cost production technique. Moreover, the final shieldingproduct must be light and easy to implement in new construc-tions as well as in existing buildings. For such reasons, wallpa-per on which FSS patterns are printed with a conductive ink isan interesting and attractive solution [12, 13]. The printingprocess must, however, be compatible with the current indus-trial printing machines that are used for large-scaleproduction, as, for example, offset printing, serigraphy,flexography, and heliography.

Unfortunately, it is more complicated to print electromag-netic conductive patterns than texts or pictures with classicalinks. The development of the ink printing process is thereforean important and essential step toward an FSS wallpaper thatneeds to be well mastered. For that, several prototypes must be

Corresponding author:P. Lemaıtre-AugerEmail: [email protected]

1LCIS, Grenoble INP – Esisar, 50 rue Barthelemy de Laffemas, BP 54, 26902 Valence,France2Centre Technique du Papier, Domaine Universitaire, BP 251, 38044 GrenobleCedex 9, France3LEMA, 882 Av. Aprıgio Veloso, Bloco CJ, Bodocongo, CEP 58.109-970, CampinaGrande, PB, Brazil4IMEP-LHAC, Grenoble INP – Phelma, Minatec, 3, Parvis Louis Neel – BP 257,38016 Grenoble, France

59

International Journal of Microwave and Wireless Technologies, 2012, 4(1), 59–69. # Cambridge University Press and the European Microwave Association, 2012doi:10.1017/S1759078711001097

realized, each one needing to be tested. This is problematicbecause of the limited size of samples. Indeed, printing trialswith real industrial machines are very costly, so a more realis-tic way is to produce the first prototypes with a semi-industrialpilot printing machine. But, often, the latter produces proto-types that are too small for an experimental characterizationin free space [5]. A previous study showed that the samplesize must be greater than the biggest wavelength considered,which approximately corresponds to a paper size A4 at2 GHz [14]. The experience of the authors showed themthat a size A3 is, however, preferable.

We thus report here on a very simple way to rapidly butpartially characterize the electromagnetic response of spatialFSS filter prototypes with a limited size. We show here thatit is possible to do measurements inside a rectangular wave-guide and moreover that the results are a good indication ofthe fabrication quality process. For FSS patterns that havetwo axes of symmetry, the measurements inside a waveguideare identical to the ones that would be done in free space ata specific angle of incidence. For FSS patterns that do nothave those two symmetries, direct comparison is no longervalid, but the comparison of the measurements with full-waveelectromagnetic simulations is an assessment tool of the print-ing quality. The proposed technique is thus a complementaryexperimental investigation tool well adapted to preliminarymeasurements during a technological development process.Measurements are rapidly done, and the prototypes pro-duction costs are decreased, thanks to their limited size.

The combined use of FSS with waveguides is not a novelidea. In fact, it is a well-known technique to realize waveguidefilter components [15–18]. In that case, the free-space responseof FSS is not considered because the FSS and the waveguide areboth considered as a single global structure during the filtersynthesis procedure. Another combined use of FSS and ofwaveguide consists in modifying the guiding conditions byadding FSS to the waveguide walls. For example, quasi-transverse electro-magnetic (TEM) waveguides were obtainedthat way [19]. However, few works reported in the literaturedirectly focus on the possibility of characterizing inside a wave-guide FSS which were originally designed for spatial filteringpurposes. Nevertheless, Hannan and Balfour in 1963–1965did a rigorous and detailed analysis of this phenomenon for aphased-array antenna [20, 21]. They studied circular patchesperiodically spaced and showed that the response inside a rec-tangular waveguide is equal to the one in free space for preciseincidence angles. They also extended this concept to triangularwaveguides [22]. Bielli et al. [23] did some FSS characterizationsin a waveguide to check the validity of the FSS model that theydeveloped. Pearson et al. [24] proposed in 1996 to extend thisconcept to numerical simulations of FSS based on afinite-element modeling. More recently (in 2003), Mias [25]reported on tunable FSS with varactors that were characterizedin free space and in a waveguide, but both measurements werenot directly compared in his work. The aim of the present studyis to show that the comparison of the measurements in a wave-guide with numerical simulations is an easy and interesting toolto check the fabrication quality of FSS, weather or not they havex- and y-axis symmetries.

The physical principle of the measurement technique isexplained and discussed in Section II. In Section III, the descrip-tion of the measurements made and of the full-wave electromag-netic simulations performed are presented. Finally, in Section IV,the results obtained for the first three FSS-groups proposed by

Munk [1] are presented and discussed. Results obtained for anon-symmetric FSS structure consisting of densely packed tri-poles are also given. Finally, experimental characterizations ofFSS with fabrication defects prove that this method is potentiallyadapted for fabrication quality assessments.

I I . P H Y S I C A L P R I N C I P A L

Like it was very well explained by Hannan and Balfour [20],even if spatial FSS are designed to work with plane waves,under certain conditions, their response when they are illumi-nated with the fundamental mode of a rectangular waveguideis identical to the one they would have in free space. Indeed,the fundamental guided mode of a rectangular waveguidecan be exactly expressed as the sum of two TEM planewaves that have identical polarizations, amplitudes, and fre-quencies but with opposite angles of incidence [26]. Now,let us consider two such plane waves in free space which areincident on an infinite and periodic structure, such as anFSS one. Interference of the two incident waves creates peri-odic null planes perpendicular to the incidence plane. For aspecific incidence angle, the periodicity of those null planesis equal to the one of the periodic structure. Moreover, ifthe density of the periodic structure elements is highenough to avoid secondary lobes or reflection, the same nullplanes are present for the reflected fields, and they arelocated at the same positions as in the incident case. For elec-tric fields that are oriented perpendicularly to the incidenceplane, perfect electric conductor (PEC) walls can thus beplaced at the positions of those null planes without any pertur-bation of the fields. In other words, there is no differencebetween a 2D infinite periodic structure illuminated withtwo incident plane waves that have opposite directions anda 1D infinite array bounded by two infinite PEC side walls illu-minated by the same two plane waves that bounce between theside walls. This equivalence is illustrated in Fig. 1(a). Finally, iftwo other PEC walls are inserted perpendicularly to the twoside walls at half-distance between two adjacent elements ofthe 1D structure, like shown in Fig. 1(b), the situation is stillnot modified. The electric fields are indeed perfectly perpen-dicular to the top and bottom PEC walls.

A possible and physical interpretation of the precedent dis-cussion is that a rectangular waveguide exited with his funda-mental mode forms two pairs of image planes in such a waythat, for the reflective elements inside it, those image planes emu-lates an infinite periodic structure. Thus, FSS patterns that havetwo orthogonal axes of symmetry (x-axis and y-axis) can becharacterized and simulated inside a waveguide. The incidenceangle at which the characterization can be done is given by [26]

u = sin−1 fc10

f

( )= sin−1 1

2f��m1

√1a

( ), (1)

where fc10 is the cut-off frequency of the guided mode TE10, f isthe frequency, m and 1 are the permeability and the permittivityof the dielectric contained inside the waveguide (air in thepresent case), and a is the largest inner dimension of the wave-guide (conventionally its width).

If some FSS patterns do not possess the two orthogonalaxes of symmetry mentioned above, their response inside awaveguide will be different than the one in free space and,

60 fabien debarros et al.

therefore, both transmission curves can no longer be directlycompared. Nevertheless, in that case, measurement inside awaveguide is still an interesting preliminary mean to assessthe fabrication quality of the metallic parts of FSS. Indeed,like it will be seen in the next section, any deviation of themeasurements from a full-wave electromagnetic simulationof the FSS inside a waveguide indicates a problem in the fab-rication process. This can be due, for example, to an enlarge-ment of the width of the conductive lines or to the presence ofunwanted open circuits or short circuits.

I I I . E X P E R I M E N T A L S E T U P A N DS I M U L A T I O N S

A) Experimental setupThe experimental setup is illustrated in Fig. 2. It consists of a40-cm-long straight-waveguide attached to two transition

sections that adapt the fields from a coaxial cable to the rec-tangular waveguide and inversely. The straight waveguideand the two transitions are commercial products from theVector Telecom company. The transverse inner dimensionsof the waveguide are 5.46 × 10.92 cm2. With those dimen-sions, the waveguide is single mode (mode TE10) from 1.37to 2.7 GHz. According to equation (1), the angle betweenthe directions of the two plane waves that constitute themode TE10 with the longitudinal direction is 36.648 at f ¼2.3 GHz and 34.888 at f ¼ 2.4 GHz.

The signal delivered from a vectorial network analyzer(VNA model 8720ES from Agilent) is coupled to the wave-guide and crosses the FSS inside it. It is then coupled backto the vectorial analyzer, thanks to the output transition.The FSS is positioned at half-length of the straight-waveguidesection. This ensures a mechanical stability of the latter duringthe measurements; the FSS are placed against a thick poly-styrene substrate of permittivity close to 1 and with negligiblelosses.

Fig. 1. Schematic representation of the equivalence principles: (a) for the PEC side walls and (b) for the top and bottom PEC walls.

Fig. 2. Schematic view of the experimental setup.

frequency-selective surface in a rectangular waveguide 61

The FSS samples are fabricated on a 0.8-mm-thick FR4substrate. In the frequency range of 1.37–2.7 GHz (i.e. single-mode region of the waveguide), the relative permittivity andthe loss coefficient of the substrate are considered invariant,and they worth: 4.3 and 0.025, respectively.

The calibration of the VNA is carried out in the followingway. First, the calibration of the reflection of each coaxial cableis done with open, short, and matched loads. The positions ofthe reference planes are thus located at the end of the twocoaxial cables. This is not problematic because phase infor-mation is not useful here. Second, the transmission calibrationis done with the two coaxial cables connected to the emptystraight waveguide.

After calibration, a transition is screwed off from thestraight-waveguide section, and the FSS (with the polystyrenesupport) is inserted in the latter. The transition is screwedback and the measurement of the transmitted power iscarried out. It worth noting here that in a preliminary exper-iment, the position of an FSS was varied along the straightwaveguide. No noticeable differences in the transmittedpower could be observed. This indicates that a good couplingexists between the coaxial cables and the transition and thatthere is no standing wave in the straight-waveguide section.This is important because, otherwise, longitudinal resonanceswould perturb the measurements. It also indicates that theevanescent modes that could be excited by the FSS decayvery rapidly and thus, do carry a negligible amount ofpower in the experiments.

B) Full-wave electromagnetic simulationsThe electromagnetic simulations were carried out with thecommercial software CST Microwave Studio. The first typeof simulations concerns the response of FSS cells inside thewaveguide. The target working frequency is 2.4 GHz. Thesize of the different FSS considered here is ranging fromapproximately 35 to 50 mm. This is slightly lower than halfof the inner dimensions of the waveguide. So, two cells of5.46 × 5.46 cm2 are simulated inside the waveguide (eachbasic cell comprises one FSS pattern). The fundamentalmode of the waveguide (TE10) is numerically excited by theinput port. The walls of the waveguide are considered to bePECs. The software is configured to compute the powercarried out by the first four evanescent modes. The

transmitted power of each mode is calculated on the outputport. No reflections are present on the ports so, like in thecase of the experiment, the length of the waveguide and theposition of the FSS have no influence on the guided power.For the evanescent modes, their decay is such that, for a dis-tance of 5 cm between the FSS and the output port, theirpower is always at least 40 dB smaller than the minimumguided power over the whole frequency range. Thus, evanes-cent modes, even if they could be excited by the presence ofthe FSS inside the waveguide, do not play a significant rolein the experiments.

The second type of simulations concerns infinite and per-iodic FSS illuminated with a plane wave. Here, only a singlebasic cell of dimension 5.46 × 5.46 cm2 is simulated withthe periodic boundary conditions. The angles of incidenceused are the ones corresponding to the ray model of aguided mode, as previously discussed in Section II (36.648 atf ¼ 2.3 GHz and 34.888 at f ¼ 2.4 GHz).

I V . R E S U L T S

A) Structures with two orthogonal symmetriesSome FSS structures that belong to the first group according toMunk’s [1] classification and that also have the two axes ofsymmetry discussed in Section II were fabricated, simulated,and tested. Munk’s FSS of the first group are patterns thatare electrically connected in their center. In the presentstudy, monopole and cross patterns were considered. Theyare illustrated in Fig. 3.

Simulations and experiment results are shown in Fig. 4.Like expected, for those two FSS patterns, the agreementbetween the simulations in free space with an incidenceangle of 34.888, the simulations inside the waveguide andthe experimental measurements are in good agreement. Theattenuation levels, the width of the band stop, and its centralresonant frequency are almost identical. In the worst case(i.e. for the cross FSS pattern), differences of 13 MHz (0.5%)and of 0.95 dB are observed at the resonant frequencybetween the experimental data and the simulations. Thosedifferences are caused by the fabrication tolerances.

The very small differences observed between the simulationresults in free space and inside the waveguide are explained by

Fig. 3. Design and dimensions of some FSS of the first group, which have symmetries along the x- and y-axis: (a) monopole FSS and (b) cross FSS.


the fact that, inside the waveguide, a frequency change causesa modification of the incidence angle. The latter is naturallydirectly taken into account during waveguide simulationsbut it is not taken into account when simulating the FSS infree space. In fact, a unique value corresponding to the inci-dence angle inside the waveguide at the resonant frequencyof the FSS was used. However, all the simulations results(Figs 4, 6 and 7) show that a strict and exact comparison isnot necessary.

Some FSS of the second group (i.e. that form a loop) withthe two required orthogonal axes of symmetry were alsostudied. More specifically, square and circular loops, bothillustrated in Fig. 5, showed very good agreement betweensimulations and experimental results. They are shown inFig. 6. Differences concerning the central resonant frequenciesare: 17 MHz (0.74%) and 1.4 dB for the worst case, i.e. thesquare loop. Those differences are observed between the free-space simulation and the measurements inside the waveguide.

Fig. 4. Simulation results in free space (incidence angle of 34.878), inside the waveguide, and experimental results for the first group FSS structures with twosymmetry axes: (a) monopole FSS and (b) cross FSS.

Fig. 5. Design and dimensions of some FSS of the second group, which have symmetries along the x- and y-axis: (a) square loop and (b) circular loop.


Finally, an example of FSS of the third group was alsosimulated. It consists of conductive square patches of51.6 mm separated by a 3 mm gap. Once again, the trans-mission attenuation coefficients obtained in free space witha periodic structure or inside the waveguide with two elemen-tary cells are in good agreement, like it is shown in Fig. 7.

The results obtained confirm the idea of a waveguide simu-lator for some FSS of the first three groups as long as they havesymmetries along x- and y-axis. FSS of the fourth group are acombination of the three preceding groups. It is thus expected

that the concept of a waveguide simulator would also beextendable to that group as long as the symmetry conditionis respected.

B) Densely packed tripole FSSA more complex FSS structure that do not present the twosymmetries discussed before was also studied. It is composedof densely packed tripoles that are made of three linear seg-ments joined at one of their extremities and making an

Fig. 6. Simulation results in free space, inside the waveguide, and experimental results for the second group of FSS with two axes of symmetry: (a) square loop and(b) circular loop.

Fig. 7. Comparison of the simulation results in free space and inside the waveguide for the square patch which belong to the third group.


angle of 1208 [27] with each other. In its infinite version, suchan FSS pattern is obtained by spatial translation of the tripolesin the same directions of the three linear segments of theinitial tripole. As can be seen in Fig. 8, a tripole is thus directlysurrounded by six other tripoles. The center-to-center dis-tance between two adjacent tripoles is equal to the length ofa linear segment plus a small additional gap, e. The great inter-est of such a structure is that its response is insensible to theincidence angle (between 0 and +608). That makes it agood candidate for spatial filtering. However, in contrast tothe previous cases studied so far, this kind of FSS has threeaxis of symmetry separated by 608. So, in the case of Fig. 8,only the symmetry with the y-axis remains pertinent.

Fig. 9. Simulation results in free space, inside the waveguide, and experimental results for the densely packed tripole FSS.

Fig. 8. Design and dimensions of the densely packed tripole FSS.

Fig. 10. Representation of three defects present on different FSS patterns: (a) enlargement of parts of the square FSS, (b) open circuit on a monopole FSS, and (c)short circuit on a densely packed tripole FSS.


Nevertheless, to further explore the possibility of character-izing such a structure inside a waveguide, a densely packedtripole FSS was simulated in free space and inside the wave-guide and its transmission attenuation in the latter wasmeasured. The results are shown in Fig. 9. Like it wasexpected, the response in free space is totally different thanthe one inside the waveguide. Free-space FSS has a single stop-band region centered at 2.32 GHz while this FSS inside awaveguide has two rejection bands at 2.03 and 2.2 GHz. Themaximum attenuation level is also changed from 240 dB to217 and to 218 dB, respectively.

The differences observed are explained by several facts. Afirst obvious reason already mentioned is the absence of thesecond symmetry along the x-axis. A second reason is dueto the mandatory presence of a gap between the end of theFSS pattern and the walls of the waveguide. Indeed, adensely packed pattern can no longer be represented by aunique unit cell and, whatever the limits are, conductivelines will always cross the chosen limits and be cut. Thus, toprevent short circuits with the walls of the waveguide, a gapis necessary. A third reason is caused by the limit-cutting pro-cedure just described which will always result in the presence

Fig. 11. Comparison of the measured transmission coefficients of a perfect structure with an imperfect one. Numerical simulation of the defect is also given: (a)enlargement of a part of the square FSS, (b) open circuit on a monopole FSS, and (c) short circuit on a densely packed tripole FSS.


of incomplete conductive parts. Each of those causes new res-onances that can be potentially visible in the frequency testregion.

The weak attenuation levels in the case of the FSS in thewaveguide are explained by the fact that only one completetripole is present for the studied pattern. A different choiceof the FSS-cell limits comprising two complete tripoleswould have presented a more important attenuation level.Another reason is the presence of the gap between the FSSand the waveguide. This space has no blocking effect andenergy is free to cross through it.

C) Waveguide simulator for the assessmentof the fabrication qualityFigure 9 also shows an interesting fact: there is an excellentagreement between the simulation of non-symmetric FSSinside a waveguide and their measurement. Thus, a waveguidesimulator could be a good and simple investigation tool for theassessment of the fabrication quality, like in the case of inkprinting on a soft substrate. Indeed, any observed differenceshave to be put on the account of a problem during the fabrica-tion or on different parameter values than the expected onesfor the substrate.

This was tested for three different cases: an enlargement ofthe FSS pattern, a small punctual absence of conductor (i.e. anopen-circuit), and a punctual short circuit between two adjacentpatterns. For a practical demonstration, all defects were createdfrom some patterns already tested. More precisely, the width ofthe two vertical lines of the square loop was enlarged with a1 mm aluminum conductive tape to create the first defect. Apart of the conductive line of the monopole FSS type wasmechanically removed to form the second defect. Finally, thethird defect consisted in short circuits between two adjacent tri-poles. This was done with the help of the aluminum conductivetape. The three defects are illustrated in Fig. 10. They representreal problems that can happen with ink printing. Measurementresults and simulations are shown in Fig. 11.

Like expected, each of these defects creates a shift of theresonant frequency from which it can be detected qualitat-ively. For the first defect (Fig. 11(a)), a frequency shift andan attenuation decrease are observed. This latter fact canprobably be explained by the fact that the electrical conduc-tivity of the added aluminum is less than the one of copper.In the last case, the frequency shift is small for the first res-onant frequency, but it is much more important for thesecond one. In all three cases considered, the main frequencyshift is greater than 130 MHz (5.5%), which is more than thedifferences observed between simulations and measurementsfor perfect circular FSS (73 MHz; 2.8%). This technique thusseems adequate for the assessment of the fabrication qualityof small samples. A more detailed study of its sensitivitywould, however, be necessary.

D) Limitations and drawbacks of thewaveguide characterization techniqueThe characterization of FSS structures inside a rectangularwaveguide has however physical intrinsic limitations. First,like mentioned previously, only the FSS patterns that havex- and y-axis symmetries and that are perfectly contained ina unit cell can be characterized. The categories of FSS

covered are thus reduced. Second, the frequency sweep islimited to the unimodal band of the waveguide. Third, accord-ing to equation (1), the angle of incidence of the fundamentalguided-mode TE10 is a function of both the frequency and ofthe incidence angle. So, inside the waveguide, it is not possibleto realize a frequency sweep at a fixed angle or to test severalangles at a fixed frequency. Testing is always done in fre-quency and in angle at the same time. However, for severalpractical cases, the angle dependence can be omittedwithout introducing a too big error. In the present study, anincidence angle of 43.48 corresponds to the frequency of2 GHz and 30.18 to 2.7 GHz. The total angle variation is13.38 for which the response of the FSS is changing veryslowly. Nevertheless, that fact may complicate the analysisof the in-guide experiments in some situations.

Other limitations not mentioned yet are to be considered.The plane wave incidence is limited to the H-plane (i.e. thexz plane in the present case) for single-mode waveguides.Oblique incidence is, however, possible with higher-ordermode waveguides but for a simple analysis, only one modeshould be excited at a time [20] which is not an easy task inpractice. Finally, the inner dimensions of the waveguidemust be an integer of the periodicity of the FSS. As thelatter are fixed for the free-space application, most likely non-standard waveguides must be used. Moreover, for differentunit cell dimensions, different waveguides must be used.

V . C O N C L U S I O N

In this paper, the principle of a waveguide simulator for spatialFSS has been presented and explained. The physical principlerelies on the fact that the electromagnetic field of two sym-metric incident plane waves is equivalent to the TE10 guidedmode of a rectangular waveguide and that the same equival-ence exist between the reflected fields. The physical interpret-ation of this is that the walls of a waveguide play the role ofmirrors with which the elementary cells inside the waveguideare duplicated. Thus, FSS patterns that have two orthogonalaxes of symmetry can be characterized at a specific angle ofincidence with few elementary cells. This assumption is con-firmed by the good agreements that exist between all exper-imental results and the full-wave simulations presented.

This characterization technique can be an interestinginvestigation tool during the development process of new pro-ducts based on spatial FSS (like an FSS wallpaper made withconductive ink printing), even if the FSS patterns are non-symmetric like it was shown. To fully know the potential ofthis technique, a detailed study of its sensitivity with respectto fabrication tolerances would have to be performed.

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[25] Mias, C.: Waveguide and free-space demonstration of tunable fre-quency selective surface. Electron. Lett., 39 (2003), 850–852.

[26] Chu, L.J.; Barrow, W.L.: Electromagnetic waves in hollow metaltubes of rectangular cross section. Proc. Inst. Radio Eng., 26(1938), 1520–1555.

[27] Pelton, E.L.; Munk, B.A.: Periodic antenna surface of tripoles slotselements. US3975738, 1976.

Fabien De Barros received his engineer-ing degree in electronics, informaticsand automatic from the Grenoble Insti-tute of Technology, in Valence, France,with a specialization in electronics ofembedded systems. During the sameyear, 2008, he also obtained a masterdegree in optics and radiofrequency

from the same university. Still with this university and withthe Centre Technique du Papier, he has undertaken Ph.D.studies that will end in 2012. His research activity includesfrequency-selective surface and their means of characteriz-ation, electromagnetic simulations, and industrial conductiveprinting technology and their means of characterization. He isusing these technologies on a paper substrate to make newwallpapers that can filter electromagnetic waves selectivelyin indoor environments.

Pierre Lemaıtre-Auger received theB.Ing. and the M.Sc.A. degrees fromthe Ecole Polytechnique de Montreal,Canada, in 1992 and 1994, respectively,in physical engineering. He obtainedhis doctoral degree in optoelectronicsand microwave from the InstitutNational Polytechnique de Grenoble,France in 1998. The same year, he

became an associate professor at Esisar, an engineeringschool of Grenoble INP, France, where he directed the phys-ical department for 8 years. He was the Director of Study ofthat school for 4 years. His first research topics were photonicsapplied to sensor applications. Since 2006, his new researchinterests are antennas and array antennas, frequency-selectivesurfaces, electromagnetic waves propagation, and localizedwaves. He is the author/co-author of more than 40 inter-national publications. In 2010/2011, he is an invited professor


at Ecole Polytechnique de Montreal to work with professorChristophe Caloz on Bessel beams.

Alysson Vasconcelos Gomes deMenezes was born in Joao Pessoa-PB,Brazil, on March 28, 1988. He is anelectrical engineering undergraduatestudent at the Federal University ofCampina Grande (UFCG). In 2009–2010, he participated to the BRAFITECprogram, which is a student exchangeprogram between Brazil and France,

supported by the Brazilian government. From January untilJune, 2010, he was with the Laboratoire de Conception etd’Integration des Systemes (LCIS), in Valence, France,where he did research on waveguides and the characterizationof frequency-selective surfaces. His interests comprise windenergy systems and telecommunications systems. Currently,he works on power electronics and control applied to windenergy systems.

Romain Siragusa was born in Paris,France. He received his engineeringand master (with honors) degrees in op-tical and radiofrequency from the Insti-tut National Polytechnique de Grenoble(Grenoble-INP) in 2006. He receivedhis doctoral degree from the GrenobleInstitute of Technology in 2009. FromSeptember 2007 to March 2008, he was

with Professor Caloz’s group at Ecole Polytechnique deMontreal as a visiting Ph.D. student. In 2009–2010, he wasa post-doctoral fellow at the Laboratoire de Conception etd’Integration des Systemes in Valence. Since 2010, he is re-search RF engineer at the Atomic Energy Commission(CEA) at Grenoble, France. His current scientific interests in-clude high-impedance surface for antenna applications andfocused phase-array antenna for RFID localization.

Tan-Phu Vuong (senior member IEEE)was born in Vietnam. He received Ph.D.degree in Microwaves from Institut Na-tional Polytechnique (INP), Toulouse,France, in 1999 and HDR (Habilitationa Diriger des Recherches) degree inMicrowave and Electronic from InstitutPolytechnique de Grenoble (GrenobleINP), in 2007. From 2001 to 2008, he

was an associate professor in microwave and wireless systems

at Esisar, an engineering school of Grenoble INP. Since 2008,he has been working as a professor at Phelma another engin-eering school of Grenoble INP. His research interests includemodeling of passive microwave and millimeter-waveintegrated circuits. His current research interests includedesign of small antennas and printed antennas for mobile,RFID, and design of passive and active millimeter-wavecomponents.

Guy Eymin Petot Tourtollet is gradu-ated in electrical engineering. From2005, he is the Director of the Depart-ment: Sensors-Modelling and DataTreatment of the Centre Technique duPapier. With his pluri-disciplinaryteam, he is in charge of developingactivities for measuring tools, modeling,data treatment and projects mixing

ITCs, and the papermaking industry. Achievements: systemsusing optics, electronics, signal and image processing, soft-ware, mechanics, hydraulics, etc. From 2010, he is in chargeof the new Strategic Priority Action devoted to printed elec-tronic using ligno-cellulosique material.

Glauco Fontgalland received the B.S.and the M.Sc. degrees in electrical engin-eering from Federal University of Paraı-ba, campus II, Brazil, in 1989 and 1993,respectively, and his Ph.D. from INPT/ENSEEIHT, France, in 1999, where histhesis work was nominated to LeopoldEscande award. From 1994 to 2006, hewas professor at CEFET-MA, Brazil. In

2003, he joined the Federal University of Campina Grandeas associate professor. From January to March 2007, he wasan invited professor at ESISAR/INPG, France. He wasawarded a fellowship by the CNPq, Brazil, in 2007. Heauthored or co-authored more than 100 research articles.Since September 2010, he is a post-doctoral researcher atThe Ohio State University – OSU, USA. His main research in-terests are electromagnetic modeling, antennas, EMC, and RFcircuits. He is the leader of the LEMA research group, inCNPq.


Characterization of frequency-selective surface spatial filters in a rectangular waveguide

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