Chapter 4: Secs ; Chapter 5: pp
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Transcript of Chapter 4: Secs ; Chapter 5: pp
Lecture 26, Slide 1EECS40, Spring 2004 Prof. Sanders
Lecture #26ANNOUNCEMENTS
• Basic Tutebot demonstration due by Fri. May 7 in lab section
• Tutebot demonstration contest on Tues., May 11, 9:30-11am, 10 Evans – possible extra credit for strong efforts. Class staff will judge.
OUTLINE• Interconnect modeling• Propagation delay with interconnect • Inter-wire capacitance• Pi model for capacitive coupling• Coupling capacitance effects
– loading– crosstalk
Reading (Rabaey et al.)Chapter 4: Secs. 4.1-4.4.4 ; Chapter 5: pp. 212-213
Lecture 26, Slide 2EECS40, Spring 2004 Prof. Sanders
Interconnects• An interconnect is a thin-film wire that electrically
connects 2 or more components in an integrated circuit.
• Interconnects can introduce parasitic (unwanted) components of capacitance, resistance, and inductance. These “parasitics” detrimentally affect– performance (e.g. propagation delay)– power consumption– reliability
• As transistors are scaled down in size and the number of metal wiring layers increases, the impact of interconnect parasitics increases.→ Need to model interconnects, to evaluate their impact
Lecture 26, Slide 3EECS40, Spring 2004 Prof. Sanders
Metal lines run over thick oxide covering the substrate contribute RESISTANCE & CAPACITANCE to the output node of the driving logic gate
Interconnect Resistance & Capacitance
VDD
GND
PMOS
NMOS
Lecture 26, Slide 4EECS40, Spring 2004 Prof. Sanders
Wire Resistance
W
LH
WLR
WHLR swire
Lecture 26, Slide 5EECS40, Spring 2004 Prof. Sanders
Typical values of Rn and Rp are ~10 k, for W/L = 1
… but Rn, Rp are much lower for large transistors (used to drive long interconnects with reasonable tp)
Compare with the resistance of a 0.5m-thick Al wire:
R� = / H = (2.7 -cm) / (0.5 m) = 5.4 x 10-2 /
Example: L = 1000 m, W = 1 m
Rwire = R (L / W)
= (5.4 x 10-2 /)(1000/1) = � 54
Interconnect Resistance Example
Lecture 26, Slide 6EECS40, Spring 2004 Prof. Sanders
Wire Capacitance: The Parallel Plate Model
WLt
Cdi
dipp
electric field lines
tdiRelative Permittivities
single wire overa substrate:
Lecture 26, Slide 7EECS40, Spring 2004 Prof. Sanders
Parallel-Plate Capacitance Example
• Oxide layer is typically ~500 nm thick
• Interconnect wire width is typically ~0.5 m wide (1st level)
capacitance per unit length = 345 fF/cm = 34.5 aF/m
Example: L = 30 m
Cpp 1 fF (compare with Cn~ 2 fF)
Lecture 26, Slide 8EECS40, Spring 2004 Prof. Sanders
Fringing-Field Capacitance
Wire capacitance per unit length:
2HWw
)/log(2
Httwccc
di
di
di
difringeppwire
For W / tdi < 1.5, Cfringe is dominant
Lecture 26, Slide 9EECS40, Spring 2004 Prof. Sanders
Problem: Wire resistance and capacitance to underlying substrate is spread along the length of the wire
Modeling an Interconnect
“Distributed RC line”
We will start with a simple model…
Lecture 26, Slide 10EECS40, Spring 2004 Prof. Sanders
Model the wire as single capacitor and single resistor:
• Cwire is placed at the end of the interconnect adds to the gate capacitance of the load
• Rwire is placed at the logic-gate output node adds to the MOSFET equivalent resistance
Lumped RC Model
Cwire
Rwire
substrate
Lecture 26, Slide 11EECS40, Spring 2004 Prof. Sanders
Cascaded CMOS Inverters w/ Interconnect
Using “lumped RC” model for interconnect:
Vin
CfanoutCintrinsic
(rwire, cwire, L)
wirewiredrfanoutwiredrintrinsicdr
fanoutwirewiredrintrinsicdrD
CRRCRRCR
CCRRCR
)()(
)(
Equivalent resistance Rdr
Cintrinsic Cwire Cfanout
Rdr Rwire
Lecture 26, Slide 12EECS40, Spring 2004 Prof. Sanders
2
)/log(2 L
HtLWL
tWHLCR di
di
di
di
diwirewire
• Interconnect delay scales as square of L
minimize interconnect length!
• If W is large, then it does not appear in RwireCwire
• Capacitance due to fringing fields becomes more significant as W is reduced; Cwire doesn’t actually scale with W for small W
Effect of Interconnect Scaling
Lecture 26, Slide 13EECS40, Spring 2004 Prof. Sanders
Propagation Delay with Interconnect
wirewiredr
fanoutwiredrintrinsicdrp
CRR
CRRCRt
)38.069.0(
)(69.069.0
wirewiredr
fanoutwiredrintrinsicdr
Dp
CRR
CRRCR
t
)(69.0
)(69.0 69.0
69.0
Using the lumped-RC interconnect model:
In reality, the interconnect resistance & capacitance aredistributed along the length of the interconnect. The interconnect delay is actually less than RwireCwire:
The 0.38 factor accounts for the fact that the wire resistance and capacitance are distributed.
Lecture 26, Slide 14EECS40, Spring 2004 Prof. Sanders
B
Wire B has additional sidewall capacitance to neighboring wires
C
Wire C has additional capacitance to the wire above it
Interconnect Wire-to-Wire Capacitance
Wire A simply has capacitance (Cpp + Cfringe) to substrate
A
Si substrate
oxide
Lecture 26, Slide 15EECS40, Spring 2004 Prof. Sanders
Wiring Examples - Intel Processes
Intel 0.25µm Process (Al)5 Layers - Tungsten Vias
Source: Intel Technical Journal 3Q98Intel 0.13µm Process (Cu)
Source: Intel Technical Journal 2Q02
k=3.6
TungstenPlugs
TungstenPlugs
Advanced processes: narrow linewidths, taller wires, close spacing relatively large inter-wire capacitances
Lecture 26, Slide 16EECS40, Spring 2004 Prof. Sanders
Effects of Inter-Wire Capacitance
• Capacitance between closely spaced lines leads to two major effects:1. Increased capacitive loading on driven nodes
(speed loss)2. Unwanted transfer of signals from one place to
another through capacitive coupling “crosstalk”
• We will use a very simple model to estimate the magnitude of these effects. In real circuit designs, very careful analysis is necessary.
Lecture 26, Slide 17EECS40, Spring 2004 Prof. Sanders
Wire 1 has resistance R1
Wire 2 has resistance R2
There are three capacitances as illustrated 1 2
substrate
C1 C2
CC
Using a simple lumped model for each wire we have three capacitances and two resistances
C1 C2
CC
R1
R2
C1 C2
CC
R1 R2
Which, when redrawn in a plane, has a “ “ shape
Pi Model for Capacitive Coupling
Lecture 26, Slide 18EECS40, Spring 2004 Prof. Sanders
Coupling Capacitance: Loading Effect
A) Coupling to grounded adjacent line
B) Coupling to floating adjacent line
C) Coupling to driven adjacent line
Case C is well-approximated to be the same as case A
Lecture 26, Slide 19EECS40, Spring 2004 Prof. Sanders
Insert the Pi model:
C1 and CC are in parallel with the input capacitance of inverter 2, Cin2.
This combined C is driven by the output resistance of inverter 1 in series with the line resistance R1
C1 C2
CC
R1 R2
21
Case A: Coupling to Grounded Line
1 2Wire 1
Wire 2
211111 inCdroutdrD CCCRRCR
intrinsic capacitance of Inverter 1
Lecture 26, Slide 20EECS40, Spring 2004 Prof. Sanders
C1 is in parallel with the series combination of CC and C2.
This combined C is driven by the output resistance of inverter 1 in series with the line resistance R1
1 2
C1 C2
CC
R1 R2
21
Case B: Coupling to Floating Line
Insert the Pi model:
2
2
211111 in
C
CdroutdrD C
CCCCCRRCR
Wire 1
Wire 2
Lecture 26, Slide 21EECS40, Spring 2004 Prof. Sanders
Signal from (1) couples to adjacent line
Insert Pi model:
1 2
3 4
4C1 C2
CC
R1 R2
21
3
Note that (4) receives both from (3) and from (1). The latter is undesired crosstalk.
Similarly, (2) receives signal both from (1) and from (3).
Let’s assume (3) is quiet, and (1) is broadcasting…
Coupling Capacitance: Crosstalk
Wire 1
Wire 2
Lecture 26, Slide 22EECS40, Spring 2004 Prof. Sanders
4C1 C2
CC
R1 R2
21
3
We want to estimate the magnitude of the crosstalk signal at the input to (4).
We cannot easily treat this problem exactly (yet), but we can see that:
1. The crosstalk signal is attenuated by the capacitive voltage divider CC in series with (C2 || Cin4 ).
2. If CC is very large, about half the signal from (1) is coupled into (4) because of the voltage divider R1+Rdr1 in series with R2+Rdr3 where Vin4 is tapped off at the center.
Lecture 26, Slide 23EECS40, Spring 2004 Prof. Sanders
Silicon substrate
SiO2
ground
1. Increase inter-wire spacing (decrease CC)
2. Decrease field-oxide thickness (decrease CC/C2)
…but this loads the driven nodes and thus decreases circuit speed.
3. Place ground lines (or VDD lines) between signal lines
Approaches to Reducing Crosstalk