Barrel EM Calorimeter Preamp / Shaper Update
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Transcript of Barrel EM Calorimeter Preamp / Shaper Update
Barrel EM Calorimeter Preamp / Shaper Update
Mitch Newcomer, Andrew Townley
Prepared for Munich Liquid Argon Week 2011
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Status April 2011
• Installed IHP’s Cadence IC6 design tools. Some issues identified with PDK but mostly OK.
• A Preamp Design and layout is near completion in IHP’s SG25H3P ( Complementary Bipolar process ).
• Alternative Preamp configurations are being considered for layout.
• Discussion underway with IHP to collaborate on measurements of their PNP devices.
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Design Overview & Constraints• Preamp constraints:
– Wide input dynamic range~70nA – 5mA (16 bit)
– Accuracy target 13 bitsPresent fixed input impedance
(25 Ω) across full range– Linear response across input
range– Variable detector
capacitance• 50pF – 1nF
– Able to drive 120 Ω resistance in shaper stage
Cdet Iin
PreampMulti Gain Shaper
Gain Selector
0ns 180ns 360ns 540ns0.0mA
0.6mA
1.1mA I(I1)
Typical input current waveform
X1,10,100
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Preamplifier
0ns 180ns 360ns 540ns1.2V
2.8V
4.5V V(out)
0ns 180ns 360ns 540ns1.2V
2.9V
4.5V V(out)
0ns 180ns 360ns 540ns1.2V
2.9V
4.5V V(out)
• Shaping depends on detector capacitance
• Increased Cdet:• Increases tpeak
• Reduces output amplitude.• Increases series noise
• Net: Increased capacitance -> worse SNR
Cdet = 50pF
Cdet = 200pF
Cdet = 1nF
Input current in above: 5mA peak
4
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Preamplifier Circuit
Rgain1800
Q2npnH3_HV
RE130
RB1
15
RC1100
RF1
20RF21.246
RSQ150
Q5npnH3_HV
RBQ1
31RE24k
R14k
C11n
D1
D
PULSE(0u ain 50n 12n 400n 1n 1)AC 0
I1 C2
1µ
L2
6n
Rext
10
Noiseless
R51000
C315p
E1
2
Noiseless
R71k
C415p
E2
20
Noiseless
R81k
C515p
C71µ
Q5
Q4
C102p
C112p
Q1npnH3_MV
RSQ2150
Q6
R1110k
Rdrop50 Q3
npnH3_HV
R1010k
Rtrim5600
R30
2
C1210p
VCC1
FBk
VCC2
VEE1
Out
shout
VCC2
VCC2
VCC2
VCC2
VFILT
VCC2
VEE1
VCC2
Out
In
a
Total Preamp Power ~ 45mW
Ideal Shaping elements
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Input Stage• Q1: minimize series
noise• Resistor feedback:• Prevent interconnect
parasitics from increasing 1.25Ω.
• Large transient feedback currents ~100mA.
Rgain1800
Q2npnH3_HV
RE130
RB1
15
RC1100
RF1
20RF21.246
R14k
C11n
D1
D
PULSE(0u ain 50n 12n 400n 1n 1)AC 0
I1
C71µ
C102p
C112p
Q1npnH3_MV
Rdrop50
Q3npnH3_HV
R1010k
Rtrim5600
VCC1
FBk
VEE1
VFILT
VCC2
VEE1
VCC2
In
vgain
a
Input feedback transistor – noise critical!
1mA
VCE = 3.6V
0.7mA
9mA
VCE = 1.5V
VCE = 1.5V
VCC2 = 5V
VCC1 = 2.5V
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Input Stage
Rgain1700
Q2npnH3_HV
RE130
RC1100
RF1
20RF21.246
R14k
C11n
PULSE(0u ain 50n 12n 400n 1n 1)AC 0
I1
C71µ
Q1npnH3_MV
Rdrop50
Q3npnH3_HV
R1010k
Rext
10
VCC1
FBk
VEE1
VFILT
VCC2
VEE1
In
vgain
a
0.0µs 0.2µs 0.4µs 0.6µs 0.8µs 1.0µs0.0mA
2.8mA
5.5mA I(I1) I(Rgain1)0.0µs 0.2µs 0.4µs 0.6µs 0.8µs 1.0µs
0.0V0.8V1.6V2.4V3.2V4.0V4.8V V(vgain) V(vfollow)
vgain
vfollow
I1
I(Rgain1)
0.0µs 0.2µs 0.4µs 0.6µs 0.8µs 1.0µs0.0V
2.0V
3.9V V(cq1,N022) V(vgain,N015)
VCE (Q2)
VCE (Q1)
50pF
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Input Stage• Layout considerations:– How to connect to feedback while having minimal
impact on resistance ratio? – Low impedance connection to input pad
RF1
20RF21.246
Q1npnH3_MV
FBk
VCC2
a
2RF1 2RF1
RF2
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Feedback resistors• Used lowest per-square
resistance available– Easiest way to achieve 1.25Ω
resistor• Less than one square of
resistance– Tradeoff: ~30Ω feedback
resistor ends up being very large
• Will be some uncertainty in 1.25Ω– Solution: only include 20Ω out
of 30Ω on chip– Externally tunable
• Split 20Ω into two parallel 40Ω– Avoid current crowding effects
600µm
100µm
360µm 60µm
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Input StageInput transistor Q1NPN_MV: Nx=8, Ny=1, m=812µm
Emitter connection: L=150µm
TopMetal1
Emitter connection: W=400µm
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Feedback resistors• RF1, RF2 set input impedance• Need to dissipate ~100mA peak
– Also must be of same type (for matching)– Width determined by power density allowance
• Max density in Rsheet larger than allowed by contact density• Possible to make addt’l contact row??
RF1
20RF21.246
Q1npnH3_MV
FBk
VCC2
a0.75 µm
(1 cont. per 0.75µm) × (0.4mA per contact) = 0.53mA/µm effective max density
Self Heating
I (mA)
Resis
tanc
e
Safe Area
Output driver• Wide ground, output connections for low
impedance.• Minimize potential for current crowding.
Q5npnH3_HV
RBQ1
31RE24k
Q4
C1210p
I1
1.5mA
VCC2 Out
a
TopMetal1 (Out)2RBQ1
2RBQ1
400µm
TopMetal1 (Out)TopMetal2 (GND)
PNP current mirror
Q4 Q4
Q5 (distributed)
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Q5npnH3_HV
RBQ1
31RE24k
Q4
C1210p
I1
1.5mA
VCC2 Out
a
Output driver
• Output driver block– PNP “inverts” voltage
signal as current– RC2 converts to voltage– Q5 draws more current
(connected to feedback point)
• Same function PNP or PMOS?– PNP Vceo Limit (2.5V)– PNP Vcbo (4V)
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Vce = 3.7V
Vce = 3.7V
0.0µs 0.2µs 0.4µs 0.6µs 0.8µs 1.0µs0.0V0.8V1.6V2.4V3.2V4.0V4.8V V(vc_pnp) V(driverin) V(out)
driverIn
vc_pnp
out
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Output driver
• PMOS, not PNP?– Higher Vbreakdown. (3.3V)
• Output impedance set by gm of PMOS
– Reduces effective overall gain when driving low-impedance of feedback
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Output driver
• PNP:– Output driver gain
0.96
• PMOS:– Output driver gain
0.73. ( First try)
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Chip level• Target: Two or
four preamps per chip:
PMOS and PNP?• Add test
structures in extra space.– Look at
breakdown, noise from different transistors.
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Summary and Plans
• IHP SG25H3P process is relatively expensive and may offer significant advantages. – PNP Vceo of 2.5V vs operating point of 3.2 to 3.7V is the only
potential issue identified with the process. Transistor is in a safe operating point but the concern is that spontaneous breakdown currents may occur adding to the amplifier noise.
– Plan to submit one or two versions of the preamp in the July 2011 run to understand this issue.
– IHP has expressed interest in working in collaborating on measurements of the radiation sensitivity of the IHP PNP transistors. Details are under discussion.