ANTENNA FEEDS AND RECEIVERS

Ben McCallMartin Marietta Corporation

Sand Lake RoadOrlando, Florida

February 1972Interim Report for Period April-November 1971

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(NASA-CR-122365) ANTENNA FEEDS ANDRECEIVERS Interim Report, Apr. - Nov. 1971B. McCall (Martin Marietta Corp.) Feb.1972 155 p CSCL 178 Unclas

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OR 11,660-1

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INTERIM REPORT

ANTENNA FEEDS AND RECEIVERS

OR 11,660-1 February 1972

Martin Marietta CorporationOrlando, Florida

CONTENTS

Summary . . . • • xi

1.

2.

3.

Introduction

Make or Buy

Hardware Development •

1

3

5

Antenna Feeds and Microwave Components •

Receiver System

Collimation Tower Equipment. . • • • .

3.1

3.2

3.3

3.1.13.1. 2

3.2.13.2.23.2.33.2.43.2.53.2.63.2.73.2.83.2.93.2.10

3.3.13.3.2

Rosman 85-Foot Antenna • •Mojave/TGS 40-Foot Antenna • •

Overview • • • • . •Cooled Parametric Amplifier • • • •Communication Down-Converter ."X9" Multiplier • • • • • •Tracking Down-Converter. • ••Performance Monitor/Frequency Translator •Miscellaneous Receiver Test Aids • • • • .Local Oscillator System. . • • •Interconnection and Cabling. . •Receiver Monitoring and Control. •

Collimation Tower Electronics.TGS Antennas and Controls.

5

530

54

5462656969758386

102118

132

132138

4. Schedule . •

iii

141

10 Band-Reject Filter (Coax) ••

Axial Ratio of Tracking Array Using 6 GHz CollimationTower Antenna. •••• • • • . • • • •

Equipment Set-up for Primary Axial Ratio Measurements.

Equipment Set-up Secondary Axial Ratio Measurements.

Secondary Axial Ratio of Tracking Array ShowingLack of 180-degree Symmetry•••••••••

1

2

3

4

5

6

7

8

9

ILLUSTRATIONS

New Rosman Feed System •

Axial Ratio of Polang Antenna.

Initial Ridged OMT Configuration.

Symmetrical Feed OMT

Prototype Diplexer • . '.

6

10

10

13

14

15

18

18

21

22

26

11 Set-up to Measure Phase-Compensating Rotary Joint Performanceat Rosman. • • . • • • • • • • . • • • . . • • • 24

12 Polang Channel Axial Ratio Including Rotary Joint Effects. • 25

13 Measured Effect of Existing Axial Ratio Alignment. • . 26

14 Measured Effect of Aligning Axial Ratio of Polang andRotary Joint • • • • • • • • • • . • . . • . •

18 VSWR of Receiver Polyrods

15 Measured Effects of Axial Ratio Alignment Over theComplete Receive Band. • • . • . • • • •

16

17

Axial Ratio of Phase-Compensating Rotary Joint Model •

New Mojave and TGS Feed System •

27

29

31

34

22

19 Measurements of Axial Ratio Null Depth and positionversus Frequency (TGS Feed). • ••••

20 Breadboard Polarizer in Test Fixture • •

21 Insertion Loss Comparison of Unmodified TGS.

Measurements of VSWR and Insertion Loss on the TGS OMT(Unmodified) • . • • • • . •

23 Monopulse Comparator

24 Insertion Loss Measurements of TGS Comparator (Unmodified)- Sum Port to Antenna Port •• ••.••• • • • • • •

v

36

37

39

40

42

43

25 Comparator VSWR Measurements (Pre- and Post­Modification). • • • • • • . • • . • • • . •

26 Comparator, Illustrating Modification Areas

44

46

27

28

Post-Modification VSWR Measurements Looking IntoAntenna Ports of Spare Comparator • • . • • • •

Post-Modification Insertion Loss Measurements ofSpare Comparator - Sum Port to Antenna Port

47

48

29 Comparator Isolation Measurements (Pre- andPost-Modification) • • • • • . • . • • • • • • • • • . . • • • • 49

30 Orientation of Antenna-Mounted Unit Portionof Parametric Amplifier • • • • • • •

31 Orientation of Antenna-Mounted Unit Portion

52

36 Polarization Error-Tracking Channel

of Parametric Amplifier

32 Receiver System - Rosman

33 Receiver System - TGS •

34 Receiver System - Mojave

35 Rosman-Mojave-TGS Communications Channels

38 Antenna-Mounted Portion of Parametric Amplifier

39 Communications Down-Converter Configuration

40 Communications Down-Converter (Only one Shownfor Clarity) •.•.••.•••

41 "x9" Multiplier Configuration

42 Tracking Down-Converter Configuration

43 Tracking Down-Converter

37 x and y Error Channels

· · · . 53

55

56

57

58

58

61

63

66

· · · . · . 68

70

. . · · · . 71

74

44 Performance Monitor/Frequency Translator Configuration • • • • • 76

45 Performance Monitor/Frequency Translator ••

46 Frequency Translator . • • • • • • • • •

77

77

48 Performance Monitor •

47 Translator Transmit-Receive Frequency CombinationsThat Provide Undesired Spurious Responses Due toLocal Oscillator • • • • • • • • •

49

50

Miscellaneous Receiver Test Aids - Rosman

AIL Type 76 Noise Source • • • • •

vi

• . 80

• • 81

84

85

51 AIL Type 137 Calibrator

52 Local Oscillator Generation System - All Sites

87

91

53 Worst Case Receiver Local Oscillator to SingleSideband Phase Noise .

54 Fluke 645A Synthesizer (Front View)

55 Fluke 6160A Synthesizer (Front View)

93

94

94

56 Single, Sideband Phase Noise Characteristics of Fluke 645A and6160A Synthesizers . 96

57 Frequency Generator

61 Intersite RF Cables - TGS

58 Front Panel of Frequency Generator

Interconnecting Cable Assemblies - All Sites

114

99

101

103

106

109

111

• • 113

• • • • . • • • • • • • • • 115

116

Junction Box Assembly

Junction Box Schematic

Power Supply Assembly

Power Supply Schematic .

Intersite RF Cables - Rosman

Intersite RF Cables - Mojave

59

60

62

63

64

65

66

75 Location of Equipment - TGS

73 CW Test Signal Multiplier switching

74 Location of Equipment in Racks - Rosman

71 Signal and Test Relays Controlled by Mode Selector Switch

72 Typical Control and Monitor Loop for Control ofTransfer Switch "G" in Paramp ••••

67 Attenuation vs Frequency Characteristicsof EMI Filters • • • . . • • • •

68 Rotary Mode Selection Switch •••••••

69 Control and Monitor Chassis Subassembly

125

• 127

128

129

• • 117

• 119

• 120

121

• 122

Control and Monitor Assembly .••.70

76 Local Amplifier Control Unit and RefrigeratorControl Unit - Rosman ••••••

77 Installation of Local Amplifier Control Unit andRefrigeration Control Unit ••••

78 Stable Source Assembly . • • • • • • • • • •

131

133

• 134

vii

79

80

81

82

83

External Attenuator Panel Assembly • .. • • • •

Collimation Tower Electronics • • • • • • • • •

Model 5616-1-5136-R Polarization positioner

Model 4112 positioner Control Unit •

Master Plan • • • . • • • • • •

viii

• . 135

• 136

•• 139

• 139

• 142

TABLES

1

2

3

Make or Buy List • • •

VSWR of Rosman Feeds •

Isolation From Communication Horn to TrackingError Ports - Rosman . • . • • • • • • •

4

8

9

4

5

6

7

8

Measurements of Axial Ratio of One Quadrant and TwoSeparate Horns Within That Quadrant

Polarizer Null position Stability

Comparator Phase Measurements

Updated Communications Channel Data

New Polang-Error Channel Data

· . 11

37

• • • 50

• • 59

. 60

• .110

• .124

· .140

and Attenuations for Each Signal. . . . . . . . . . . . . . . . . . . . · · ·104

and Attenuations for Each Signal. . . . . . . . . . . . . . . . . . . . · · .108

and Attenuations for Each SignalCable LengthsPath - TGS •

Test/Operate Mode Truth Table

Collimation Tower Antenna Performance

14

15

13

12 Cable LengthsPath - Mojave

9 Angle Tracking-Error Channels • • •• ••• 61

10 Frequency Translator LO Frequencies and Second Harmonics • • • • 78

11 Cable LengthsPath - Rosman

ix

PRECEDING PAGE BLANK NOT ~':AOZ

SUMMARY

This report describes the results of 7 months of study, tradeoffs,test design, and fabrication in connection with the NASA Contract NASS­2l6lS to modify three ground stations in support of the ATS-F program.

As a result of tests on the existing feed system of the Rosman No. 28S-foot antenna and on the Transportable Ground Station (TGS) 40-footantenna, it was determined that modifications of the existing phase­compensating rotar1 joints at Rosman are feasible. It was also confirmedthat other components, such as the orthomode transducer, must be completelyreplaced, as indicated by NASA test data. In the TGS 40-foot antenna feedsystem, it was found to be feasible to broadband the existing monopulsecomparator by adding simple irises and posts; both spare and activecomparators have been modified. Likewise, it was demonstrated that theTGS polarizers can be broadbanded by adjusting existing pins and addingtwo new pins. These modifications are also directly applicable to theMojave 40-foot antenna.

A subcontract was let for the design and construction of a new ortho­mode transducer for Rosman. Preliminary tests on the new design indicatethat it will meet all requirements of the modified system, although weightof the new unit is high.

A tradeoff of cost factors indicated the desirability of subcontractingthe receiver down-converters associated with the new communications andtracking receiving systems, and these units are now under construction andwill be ready for integration into a system .for preliminary acceptancetests at Orlando. Such tests are expected to be completed for the Rosmansystem in time for shipment to Rosman, North Carolina on or about April 1,1972.

This report gives detailed electrical and mechanical characteristicsof the new equipment as well as installation plans to enable NASA and itsother contractors to determine the aaequacy of the designs and to confirmthat planned locations are both available and compatible with plannedoperational concepts.

A summary of remaining activities is given, showing the expected com­pletion of procurement and fabrication in January of 1972. Subsequently,in-house preliminary system acceptance tests will be performed, followedby on-site installation and final acceptance tests. The schedule showsdetailed steps remaining to achieve on-time performance of all contractmilestones.

xi

1. INTRODUCTION

This report describes progress to date in the design and implementa­tion of modifications to feeds and receivers under Contract NAS5-2l6l5.The contract requires modifications to three ground receiving stations toincrease frequency coverage from the present 3.9 to 4.2 GHz to a newcapability of 3.7 to 4.2 GHz. The modifications will also increase opera­tional flexibility by providing a double conversion receiving system inwhich preselection filters need not be switched and in which frequencyselection is performed by digitally controlled frequency synthesizersproviding better than 1 kHz resolution over the 500 MHz range. The contractalso provides for a new wideband cooled amplifier having a noise tempera­ture of less than 18 degrees K. The contract provides for miscellaneousadditions to, or improvements in, test or calibration features and providesfor limited refurbishment of feed cone mechanical condition at Mojave andTGS.

This document reports the measurements made on the existing Rosman85-foot No.2, Mojave 40-foot, and Transportable Ground Station (TGS)40-foot antennas and receiving systems. It presents the conclusionsreached regarding necessary changes and describes implementation plannedto achieve increased bandwidth capability and other features required byNASA GSFC Specification S-57l-P-35. This document also describes designswhich will implement Contract Amendments 1 through 6.

This report supplements the Design Review Report, OR 11,239, datedAugust 1971 with particular emphasis on test results and actual hardwaredesign information including electrical specifications, planned locations,and dimensional data which will be useful to NASA and its support contractorsin verifying that space is available, that the equipment will perform thefunction intended, that the operational layout will be functionally feasible,and that the new equipment will interface with other planned equipmentbeing provided by or relocated by other contractors.

Finally, the report delineates the expected schedule of events throughcompletion of the contract in December 1972.

1

2. MAKE OR BUY

From Table 1, which summarizes the make/buy decisions that have beenmade and implemented for the contract, it can be seen that the preponder­ance of equipment is purchased by Martin Marietta. These decisions weremade on the basis of the most advantageous arrangement to the Government.

As expected, it has proved more economical to procure from othervendors and contractors those items that dovetail with their existingproduct line or closely relate to their most predominant product line.Thus, such waveguide components as orthomode transducer, diplexers, andbandpass and reject filters have been subcontracted to WaveCom; cooledamplifiers to Comtech; and down-converters to Aertech. Off-the-shelffrequency synthesizers have been procured from the John Fluke ManufacturingCompany.

Martin Marietta has chosen to build those assemblies which arepeculiar to this contract: collimation tower stable sources, receivercontrol panel, junction box, power supply assembly, etc. or which, bytheir similarity to equipment built on other contracts, made it obviousthat significant engineering labor wo~ld be saved by adapting existingdesigns. Thus, the frequency generator panel, which is nearly identicalto those built for the ATS-F transmitters (Contract NASS-21198), is beingfabricated in-house.

With the exception of the down~converters, all of these decisionshave followed. the proposed contract execution plan. In the case of thedown-converters, rigorous competition, from both within and outside theMartin Marietta Corporation, made a clear-cut case for the subcontract.It is believed that the prevailing business climate throughout the industryat the time of the subcontract resulted in a unique opportunity for MartinMarietta to provide the Government with the required equipment at veryreasonable cost.

3

TABLE 1

Make or Buy List

MAKE

BUY

Frequency generatorControl and monitor panelstable sources unitJunction boxPower supply assemblyCoaxial cablesTen-conductor cables55 -conductor cablesRework TGS antenna assemblyRework Mojave feed assembly

Ref. MM Drawing No.

614-01560614-01575614-01574614-01690-2614-01610

Supplier

Cooled amplifier systemCommunications down-converterTracking down-converter assemblyMultiplier assemblyPerformance monitor/frequency translatorOrthomode transducerDiplexerTransmit reject filterTransmit reject filterTunnel diode amplifierSolid state sourceSynthesizersSynthesizersTransmit waveguide switchCoax transfer switchCoaxial direction coupler (30 dB)Directional coupler coax (20 dB)Directional coupler coax (10 dB)TWT amplifierStable sources multiplierStable sources

4

614-01513614-01525614-01526614-01518-A614-01543614-01508614-01510614-01511614-01512614-01516614-01535614-01500614-01540Logus L05-228Logus L07-232614-01547614-01547614-01547614-01520614-01519614-01521

ComtechAertechAertechAertechAertechWaveCommWaveCommWaveCommWaveCommAertechAILFlukeFluke

NardaNardaNardaVarianGreenrayGreenray

3 . HARDWARE DEVELOPMENT

3.1 Antenna Feeds and Microwave Components

At the Bidders' Conference of December 1969, a data package presentedto each prospective contractor showed the measured performance from 3.7 to4.2 GHZ for selected assemblies and components of the Rosman and Mojavesystems to assist the contractor in deciding the extent of modificationand/or replacement necessary to render the system useful over theextended frequency band. It became obvious that all microwave components(such as filters, diplexers, and orthomode transducers (OMT's) wereinitially designed for maximum performance in the 4.0 to 4.2GHz band andthat rapid rolloff in out-of-band performance made it necessary to replacethese components to employ a broader portion of the band.

This section reports on on-site and in-house measurements made on thefeed system since contract award. This data was taken from specific com­ponents and subassemblies to confirm the need for replacement or modifi­cation and to serve as a baseline, or pre~od reference. Those modifica­tions already made to some feed components are discussed here, as well asthe performance of new components and plans for completing the feed modi­fication.

Modifications to the Mojave, TGS, and Rosman feeds will have verylittle impact on the gain and noise temperature performance of thosesystems, other than the normal degradation that could be expected fromextending the receiving frequency band down to 3.7 GHz. (The inherentprimary beam broadening, experienced as frequency is lowered, causes sub­reflector spill-over, which leads to lower illumination efficiency,highersidelobes, and a slight increase in noise temperature.) Each ofthese characteristics is a direct function of the feed apertures, whichwill not be altered in this program. All items to be replaced or modi­fied (such as the OMT, diplexers, filters) will have insertion loss andVSWR characteristics equal to or better than those of the existing equip­ment; therefore, they will not contribute to an increase in noise tempera­ture or a decrease in gain.

3.1.1 Rosman 8S-Foot Antenna

A block diagram of the Rosman microwave configuration to be con­tained in the feedcone is shown in Figure 1. Essential features of thesystem are:

1 Use of a single horn for transmit, receive, monopulse sumchannel, and polarization sensing

2 Use of a circularly polarized ring array for the monopulse errorchannels

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3 Polarization sensing on the null in the orthogonally polarizedreceive input

4 Automatic polarization sensing and alignment over a 270-degreesector

5 Extraction of the beacon signal for the monopulse sum channel afteramplification, and use of a phase-compensating rotary joint tomaintain relative phase with the circularly polarized errorchannel array

6 Capability to transmit parallel or perpendicular to the polari­zation of the receive signal

7 Low-noise cooled amplifier

8 Filters to isolate the transmitter from the receivers

9 Ability to inject test signals (CN or noise)

10 Capability to extract an RF signal (prior to down-conversion)and send it directly to the Instrumentation Building via alow-loss elliptical waveguide for RFI experiments.

Comparison of the existing microwave system at Rosman with the newsystem shows that operation and capabilities are essentially the same,the prime difference being performance of the individual components. Themajor exception to this is replacement of the paramp amplifier TNT com­bination with a parametric amplifier/transistor amplifier combinationand alteration of the test signal injection circuits.

3.1.1.1 Communication Feedhorn and Tracking Array

A series of measurements was performed on the communications feedhornand tracking array, including the comparator network, to determine theirutility over the new operating frequency band. VSWR measurements on thecenter (communications) feedhorn, using a WR187 slotted line and a taperedtransition from.WR187 to the 1.8 inch square horn input (Table 2) showthat the horn will operate down to 3.7 GHZ. No VSWR measurements weremade in the transmit band from 5.925 to 6.425 GHz because the requiredtransition from WR137 to 1.8 inch square was not available. Since thehorn was initially designed to operate from 5.9 to 6.4 GHz, however, nodifficulty is anticipated. VSWR measurements of the tracking array(Table 2), using a coaxial slotted line directly at the AX and AY outputsterminals of the comparator networks, show that the tracking array is wellmatched over the receive band, except in the immediate vicinity of 3.7GHz where the VSWR is a maximum of 1.6:1. This performance is consideredacceptable since it will not noticeably degrade the tracking performanceof the Rosman antenna.

7

TABLE 2

V5WR of Rosman Feeds

Frequency Communication fiX fly

(GHz) Horn Output output

3.60 1.18 1.48 1.203.65 1.21 1.603.70 1.13 1.05 1.063.75 1.53 1.453.80 1.06 1.32 1.333.85 1.35 1.263.90 1.06 1.32 1.123.95 1.23 1.144.00 1.02 1.05 1.154.10 1.15 1.15 1.154.20 1.10 1.20 1.27

Isolation measurements were made between the communications horn andthe error channels by inserting the transmitter frequency signals into aWR187 wavegide-to-coax transition connected to the communications hornthrough the tapered transition~ VSWR of this setup was 1:04 to 1 at 6.1GHz. The measured isolation (Table 3) was in excess of 50 dB over theentire transmit band, although in most cases it was in excess of 70 dB,the measurement limit of the instrumentation.

Several attempts were made to measure the secondary axial ratio ofthe tracking array~ the best data presently available, however, indicatesthat the axial ratio may be less than 3 dB over the receive band from4.0 to 4.2 GHz. In the band from 3.7 to 4.0 GHz, it appears that the axialratio degrades to a maximum of 6 to 8 dB. The high axial ratio in thetracking horns has a definite effect on the angle-tracking performance ofthe antenna by adding pre- and post-comparator phase errors.

On 19 and 20 May 1971, an attempt to measure secondary axial ratiowas hampered by equipment problems. Resulting data led to the suppositionthat the dichroic subreflector may be partly responsible for the highsecondary axial ratios. Details of these data, measurement techniques,and problem details were reported in the Design Review Report, OR 11,239,August 1971, pages 25 to 29.

8

TABLE 3

Isolation From Communication Horn toTracking Error Ports (Rosman)

Transmitted Isolation (dB)Frequency (GHz) LlX LlY

5.9 > 70 >706.0 >70 >706.1 63 636.2 54 566.21 50 516.22 55 566.25 > 70 >706.3 > 70 >706.4 > 70 >70

On 10 and 11 August 1971, a renewed attempt to measure the axialratio of the tracking array also met with limited success. It was decidedto measure first the primary axial ratio of the array, using the polariza­tion calibration horn mounted in the subreflector. (The dichroic subreflec­tor was replaced by the original all-metal unit to measure effects, ifany, on the axial ratio.) The equipment setup for these primary measure­ments is shown in Figure 2. Due to the on-axis null generat~d by thecomparator network, as seen at the LlX or LlY channel output, it was notpossible to measure the axial ratio of the complete array. Instead, theaxial ratio of one quadrant and two separate horns within that quadrantwere measured (Table 4). Also shown in the table is the axial ratio ofa spare tracking horn measured at Martin Marietta's anechoic chamber.

The spare horn data shows that the axial ratio is good in the originaldesign band from 4.0 to 4.2 GHZ, but exhibits significant degradation inthe neighborhood of 3.7 GHz. The on-site measurements of individual hornswere not so conclusive, although quadrant measurements show a definitetrend toward a degradation of axial ratio toward 3.7 GHz. Unlike earlierattempts to measure the axial ratio, this data was consistent and repeat­able.

Another attempt was.· then made to measure the secondary axial ratiofrom Bald Knob Tower. Due to the very low grazing angle, ground reflec­tions were considered a possible cause for measurement anomalies; however,equipment problems overshadowed those considerations at the time. Thesetup for the secondary measurements (Figure 3) was essentially the sameas for primary measurement except the calibration horn was replaced with

9

SI~AL

GENERATOR TWT

SUBREFLECTOR

-- CALIBRATED LINEAR HORN

DIRECTIONAL·COUPLER

FREQUENCYCOUNTER

TRACKING........ ........ HORNS". ".

.............. ..""."""---- .............-----WIDEBANDRECEIVER

PATTERNRECORDER

Figure 2. Equipment Se t:-Up for Primary Axial Ratio Measurements

SIGNALGENERATOR

85-FOOT DISH

POWERMETER

~x

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4GHzDISH

CCW CWo

CD fO\

CONTROL PANEL

COLLIMATION TOWERBALD KNOB

WIDE BANDRECEIVER

PATTERNRECORDER

Figure 3. Equipment Set-Up Secondary Axial Ratio Measurements

10

TABLE 4

Primary Axial Ratio of Rosman

Tracking Feed Horns

4 Horns North Horn South Horn Spare HornFrequency North Quad. West Quad. West Quad. at Martin

(GHZ) (dB) (dB) (dB) (dB)

4.2 1.8 3.0 1.3 1.5

4.1 2.5 5.4 4.5 1.5

4.0 2.3 2.3 3.7 0.0

3.9 3.4 1.9 6.2 4.0

3.8 4.6 2.7 4.3 6.0

3.7 4.6 5.8 8.5 8.0

11

a 6-foot reflector. Due to the capability to remotely rotate the polari­zation of the 6-foot antenna with synchro position data available atthe base of the tower, it was possible to record the axial ratio onchart paper. As a result, it was possible to detect other anomalies inthe measured data, which earlier could not be seen.

Initial measurements again displayed a very high axial ratio in thedesign band from 4.0 to 4.2 GHz. Close examination of the data (Figure4) shows a definite lack of pattern sYmmetry, e.g., the change from amaximum to a minimum response should be smooth and periodic every 90degrees. Instead, the signal was erratic and not periodic.

In an attempt to determine the cause of this data irregularity, theaxial ratio of the Polang channel was measured using the identical setup.The Polang horn was linearly polarized and should have shown nulls morethan 35 dB below the peak. Examination of the measured pattern (Figure5) shows not only deep nulls but also irregular peaks which could becaused only by ground reflections and/or a misaligned rotating boresightantenna.

TO investigate the effect of the latter possibility, the testsignal was rerouted through the 6 GHz (4-foot) reflector located just be­low the 4 GHz reflector on the collimation tower. This data (Figure 5)was excellent since it displayed the deep nulls and periodic functioncharacteristics of a linearly polarized antenna. At this point, theaxial ratio of the tracking horns was measured again using the 6 GHzreflector. The limited data measured (Figure 6) was also excellentsince measured axial ratios were about 3 dB; even more importantly,the data for the first time displayed the periodic function characteris­tics of the polarization pattern. rt was not possible to make measure­ments below 4.1 GHz due to cutoff characteristics of the 6 GHz horn.

These measurements show that there is in the 4 GHz antenna a problemwhich is probably a combination of aligning the feed in the dish andaligning the dish with the Rosman II antenna. When a NASA program, imple­mented to refurbish and realign the collimation tower antennas, is completed,another attempt will be made to measure the axial ratio of the trackingarray.

3.1.1.2 High Power Switch and Rotary Joint

The high power switch, currently employed in the feed system to switchthe transmit signals between the two diplexers, will be retained in itspresent form and will continue to perform the same function. The waveguiderotary joint, which is contained at the base of the rotating table withinthe feedcone and which transfers the high power transmit signal from thestationary transmitter to the rotating feed, will also be retained as is.Both of these units have been designed to cover the transmit band from5.925 to 6.425 GHz and, although no specific measurements were made toconfirm their performance, the current and continuous use of these com­ponents in the system is evidence that their performance is satisfactory.

12

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AXIAL RATIO OF TRACKING ARRAY

Figure 4. Secondary Axial Radio of Tracking Array Showing Lack of180-Degree Symmetry

13

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4.1 GHz

-------.......

401800

4.2 GHz

i .---

:-

301800

o

..-co .310IXLLI3o0-

LLI>-~:5120~

Figure 6. Axial Ratio of Tracking Array Using 6 GHz Collimation TowerAntenna

15

Prior to reinstallation of these units into the modified feed, they willbe cleaned and tested for performance over the band.

3.1.1.3 Components to be Replaced or Modified

In the communications and Polang channels, the present OMT, transmit­receive diplexer, and transmit-reject filter will be replaced by unitsdesigned to operate over the new frequency band. The present image-rejectfilters are not required because Martin Marietta is employing the double­conversion approach, which places the image far below the passband oftransmit-reject filters and of bandpass filters in the down-converters.In the tracking error channels, the present transmit-reject filters willbe replaced by units designed for the new frequency range.

A short section of flexible waveguide will be employed in all longwaveguide runs to relieve any stresses and strains and avoid cracking ofwaveguide components. In the transmit waveguide run, the only changewill be addition of another high power waveguide switch to connect eitherof the two transmitters. Previously, both transmitters could be usedsimultaneously, if desired, by employing a diplexer. This switch will belocated in the immediate vicinity of the transmitters, leaving only onewaveguide run into the feed cone.

The phase-compensating rotating joints, presently optimized for the4.0 to 4.2 GHz receive band will be redesigned for operation over thenew frequency range. Coaxial directional couplers will be provided andcalibrated over the new frequency range. Three waveguide and two coaxialswitches will be added to check performance and to aid in troubleshooting.

The parametric amplifier, tunnel diode amplifier, and test circuitswill be covered in other sections of this report.

3.1.1.3.1 Orthomode Transducer (OMT)

The OMT is a device comprising an antenna port, through port, andside port. The antenna port mates with the communications horn input,while the other two ports mate with the antenna port of the transmit­receive diplexers. All ports of the OMT are used for transmitting andreceiving RF energy.

A new OMT is being designed, developed, and fabricated by Wavecom,Inc., Northridge, California, under subcontract to Martin Marietta.Specifications being used to govern OMT design and ultimate performanceof the OMT are summarized below:

Transmit frequency bandReceive frequency bandTransmit powerIsolation (through port to

side port)

16

5.925 to 6.425 GHz3.70 to 4.20 GHz16 kW, CW40 dB minimum

Isolation (side port tothrough port)

Insertion loss (through portto antenna port and antennaport to through port)

Insertion loss (side port toantenna port and antennaport to side port)

VSWR (transmit and receive)

40 dB minimum

0.05 dB maximum

0.05 dB maximum

1.15:1 maximum

Wavecom's initial OMT design (Figure 7) employed a ridge-loadedwaveguide into which a wave is inserted in a plane having its E- fieldnormal to the surface of the ridges. The wave is then guided into a simi­lar orthogonal section of waveguide. The use of a ridge waveguidecreates a broadband device having very low loss and capable of handlingthe high power. As the design became more detailed, the ridges were mademore symmetrical and an orthogonal set of ridges was added. The initialdesign concept intended that the ridge section would generate only thedesired TEIO mode, even though the TEll mode could be supported (ifexcited) in the band from 5.9 to 6.4 GHz. This thinking was partiallycorrect. Measurements on the breadboard model showed a significantamount of energy converted to the TEll mode at the junction where theorthogonal ridged waveguide enters the main body of the OMT. Althoughexact measurements were not made to determine the frequency responsecharacteristics and magnitude of the TEll mode, the evidence was conclus­ive that it existed and was causing high insertion loss, high VSWR, andsignificant cross coupling.

The OMT design has been changed to a symmetrical orthogonal feednetwork (Figure 8). This configuration comprises a main body withfour ports: antenna port, through port connecting to the diplexer,and two symmetrical orthogonal ports combined and coupled to the seconddiplexer. The combining network is composed of E-plane and H-plane bendsmachined to hold 1.8 by 0.740 inch I.D., and a power combiner thatresembles a Majestic tee. This combiner will be capable of matchedperformance over the entire receive and transmit band. Logic behindthis design is that the symmetrical orthogonal feed will provide a self­cancelling mechanism for elimination of the TEll mode.

A breadboard "half section" of this new design has been built andsuccessfully tested for matching on the orthogonal port. A full sectionunit has also been built and matched in the thru port. The combiningnetwork, when completed, will be attached to the main OMT body, matched,and tested as a complete unit.

17

:[1]:• • •

[

/

RIOGE-lOAOCO S£CTlmf

:~:• • •

:~:•••

-

-

Figure 7. Initial Ridged OMT Configuration

Figure 8. Symmetrical Feed OMT

18

3.1.1.3.2 Transmit-Receive Diplexer

The transmit-receive diplexer is a three-port device which serves tocouple the transmit and receive signals to the antenna through the OMTWhile maintaining isolation between the transmit and receive ports. Thediplexer consists of a T-junction with a high-pass filter in the transmitarm and a separate transmit-reject filter in the receive arm.

The present unit is designed to operate from 3.992 to 4.200 GHz.in the receive band and from 6.000 to 6.425 GHz in the transmit band.Transmit-to-receive isolation is 100 dB minimum and receive-to-transmitisolation is 40 dB minimum. Maximum VSWR is 1.15: 1 in the appropriatefrequency bands for the input ports. Insertion loss is 0.075 dB in thetransmi t arm and 0.10 dB in the receive arm. The present unit will notoperate over the new frequency band with the high isolation and low VSWRrequirements .

A new diplexer has been designed and developed and is currently beingfabricated by Wavecom in accordance with Martin Marietta Specification614-01510 summarized below:

Transmit frequency band 5.925 to 6.425 GHz

Receive frequency band 3.70 to 4.20 GHz

Isolation (transmit to receive) 100 dB minimum

Isolation (receive to transmit) 40 dB minimum

Insertion loss (transmitter port to antenna port) 0.1 dB maximum

Insertion loss (antenna port to receive port) 0.1 dB maximum

Transmit power 16 kW, CW

VSWR (any port) 1. 15 : 1 maximum

Delay distortion (unequalized):

Linear component

Parabolic component

Residual ripple

19

0.3 nanosecond/40 MHz maximum

0.025 nanosecond/MH z2 maximum

0.3 nanosecondpeak-to-peakmaximum

Wavecom's design is based on a high-pass filter in the transmit armand a band-reject filter in the receive arm. The high-pass filter iscomposed of a special cross section of waveguide designed to have a cut­off frequency of 4.8 GHz. The length of this section is selected to givethe required attenuation to signals in the receive band, while maintainingthe lowest possible insertion loss to signals in the transmit band. Theband-reject filter comprises a section of ridge-loaded waveguide to whichan appropriate number of resonators are included to provide the requiredrejection to the transmit frequencies while maintaining the lowest possibleinsertion loss at the receive frequencies. The total configuration of thediplexer (Figure 9) includes the necessary waveguide transitions tomate with WR159 waveguide at the transmitter port, WR229 at the receiveport, and 1.800 x •740-inch waveguide at the GMT port.

In the design process, each filter was developed separately and thencombined to complete the diplexer. The complete prototype diplexer wastested to give the following performance:

VSWR = 1.05 maximum (5.925 to 6.425 GHz)

= 1.07 maximum (3.7 to 4.2 GHz)

Insertion = 0.025 dB - GMT to transmi tterLoss

= 0.11 dB* - GMT to receiver

Rejection > 50 dB - 3.7 to 4.2 GHz in transmit port

>100 dB - 5.925 to 6.425 GHz in receive port

3.1.1.3.3 Band-Reject Filters (Error Channels)

A band-reject filter is provided in each of the two tracking-errorchannels to prevent the transmit signal from interfering with the /::,X and /::,y

channels. Transmit-receive isolation in these channels is the sum ofthat provided by these filters, plus the decoupling of the transmit andreceive signals through use of separate tracking antennas. The presentsystem employs filters that provide 160 dB minimum isolation to the trans­mi t frequency. The specification requires that 100 dB isolation be main­tained in both channels. Measurements on the feed system recently performedat Rosman indicate that the isolation between transmit feed and trackingfeed is at least 50 dB. In addition, past experience has shown that bothMojave and TGS operate satisfactorily with only 100 dB isolation. Basedon these considerations, a new filter specification has been written which

* The model is made of copper and brass materials soldered together.The final unit is expected to have a maximum insertion loss of 0.07 dBin the receive band.

20

....

...

...

...

...

...

Figure 9. Prototype Diplexer

requires 90 dB isolation be achieved from the filters alone. Thus aminimum of 140 dB of isolation will be realized.

A new filter has been successfully designed, developed, and fabricatedby Wavecom in accordance with Martin Marietta Specification 614-01511,summarized as follows:

...

Transmi t (reject band)

Recei ve (pass band)

Insertion loss (reject band)

Insertion loss (pass band)

VSWR (pass band)

5.925 to 6.425 GHz

3.70 to 4.20 GHz

90 dB

O. 35 dB maximum

1.15:1 maximum

...

-

Initial specifications for this filter required less than 0.15 dB ofinsertion loss, which limited the design to a waveguide configuration. A

brief study on the need for such a low insertion loss, and a trade ofsystem performance, size, weight, cost, reliability, and installationproblems, resulted in ultimate selection of a coaxial yersion of the filter.The first copy of this TEM interdigital filter (Figure 10 has beendelivered to Martin Marietta. The following summarizes its performance:

VSWR

Insertion loss

Rejection

1.16 maximum (3.7 to 4.2 GHz)

0.35 dB maximum (3.7 to 4.2 GHz)

90.2 dB minimum (5.925 to 6.4 GHz)

21

-

Figure 10. Band-Reject Filter (Coax)

3.1.1.3.4 Phase-Compensating Rotary Joints

The Rosman feed system contains two phase-compensating rotary joints,one in the sum channel after the parametric amplifier and the second inthe Polang line. The need for these rotary joints is to provide a phaserotation identical to that experienced in the circularly polarizedtracking horns for an incoming linearly polarized signal. The phase­compensating rotary joint in the sum channel is needed to establish a(relatively) fixed sum phase reference to which the tracking error signalis compared for direction. As the sum channel needs to be phase compensa­ted to be compatible with the tracking horns, the Polang error signal mustalso be phase-compensated because it is also compared to the phase of thesum channel for direction.

Each rotary joint is made up of three sections: an input transitionfrom rectangular waveguide or coax to circular waveguide, a quarter wavephasing section to provide circular polarization within the rotary joint,and an output transition from circular waveguide back to coax. The twotransition sections are designed to maximize the coupling from the

22

-

-

transmission line to the rotary joint and to provide isolation betweenthe LCP and RCP output ports on the sum channel rotary joint. Perfor­mance of these transitions is not considered to be extremely critical tointended performance of the joint. The quarter wave differential phaseshifter is the most critical section of the rotary joint. It is essentialthat the axial ratio of the elliptically polarized wave, produced by thequarter wave section, remain better than 2 dB over the entire band from3.7 to 4.2 GHz. If the axial ratio becomes too great, both the antennatracking system and the Polang system will experience a loss in signaland tracking non-linearities.

The Rosman Polang channel data measured by NASA and distributed atthe Bidders' Conference on 16 December 1969 illustrates the effects of apoor axial ratio in the rotary joint. This data included the entirePolang channel through the rotary joint. On 20 May 1971, the rotaryjoints, sum and Polang, were removed from the feed, and bench tests forVSWR, axial ratio, and wow showed a trend toward increasing axial ratiooutside the original 4.0 to 4.2 GHz design band. This data substantiatesthe data NASA provided to the bidders; high wow and VSWR below 4.0 GHz isbelieved to be related to the high axial ratio.

On 10 August 1971, additional tests were made at Rosman to furtherevaluate the need for modifying the rotary joints. The setup employedfor making measurements is shown in Figure 11. The first set of datawas derived from using the entire Polang microwave line, including theOMT, diplexer, and rotary joint. This data (Figure 12) was identicalto that given out at the bidders' briefing with one exception: the nullposition did not shift as a function of frequency. A review of factorscontributing to the measured data showed that a null shift is not possible;hence, the apparent shift must have been caused by alignment errors orbacklash in the various drive mechanisms involved in the measurement.

In the Design Plan (OR 11,239, pages 18 through 20), the cause ofaxial ratio asymmetries measured at 3.7 GHz was hypothesized to be thearbitrary alignment of axial ratio minima of the GMT and rotary joint.This hypothesis has proved to be correct and is illustrated by thesequence of measured data given in Figure 13. This figure shows theaxial ratio of the Polang channel prior to entry at the rotary joint andthe axial ratio of the rotary joint alone. (Note that the angularreference on all data is fixed and absolute). Finally, this figureillustrates the result of combining these effects as in normal operationof the Polang system. Further measurements at 3.7 GHz showed that analignment of the minima (Figure 14) will produce a symmetrical axialratio without inflections. This alignment was shown to provide symmetryand lineari ty throughout the frequency band from 3.7 to 4.2 GHz (comparedata in Figures 12 and 15) .

Even though the "minima alignment experiment" was successful ineliminating asymmetries, it was decided to modify the rotary joints,

23

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-Figure 11. Set-up to Measure Phase-Compensating Rotary Joint Performance

at Rosman

24

4 1 GHz...~ V "i\ I i\

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40

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Figure 12. polang Channel Axial Ratio Including Rotary Joint Effects

25

,,LEGEND:

'----~-'-- ROTARY JOINT--- - -- POLANG ONLY--COMPLETE

10So 72° 36° 0° 36° 71o lJSO 144° 1 0° 14;1"40 ;:...-..:.:...-...:.:....--iDt-----=..;·~----i'~----_Dr----'

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30

Figure 13. Measured Effect of Existing Axial Ratio Alignment

101-----4----4-~-+-~~~-__+_--_+_-~~~__t--__t

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~~3:J::6_0_.....:..;72...' 0_......:.;10:.;::8;.,.0__1....4!l,,;..0_-..-o11ii~o...---;1..;..4~ 0

Figure 14. Measured Effect of Aligning Axial Ratio of Polang and,Rotary Joint

26

4.2 GHz 4.1 GHz

-~L-..

V .........

\ I l\..~ V ~

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,0:::LLI3o0...LLI>-I-<C--'LLIa::

40

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4.0 GHz 3.9 GHz-~ V 100- i'\1\ I\.,! \

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1\\ I ~

1

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Figure 15. Measured Effects of Axial Ratio Alignment Over theComplete Receive Band

27

based on the unavoidable loss of signal in the tracking sum and Polangchannel when the incoming signal is aligned with that polarization whichproduces a minimum response in the rotary joint. This post-amplifiersignal loss could amount to the axial ratio's maximum value, which is 10 dBat 3.7 GHz. The effect of this signal loss is to upset the signal balancebetween sum and error channels in the antenna angle tracking and Polangreceivers. In addition, the VSWR of the rotary joints below 4.0 GHz aremuch too high and would require at least a modification to those componentsthat would improve the match.

Plans for implementing these modifications are limited to redesignof the input and output ports for a broader band impedance match andredesign of the gO-degree phase-shifting section to enable response overthe entire receive band from 3.7 to 4.2 GHz. No change will be made tothe rotating components and outside configuration.

More specifically, when the Rosman antenna is shut down for modifi­cation, the rotary joints will be returned to Orlando for modificationand testing. The current gO-degree phase-shifting section, consisting ofsix irises, will be removed and replaced with an array of four to fivepairs of pins. The coaxial-to-waveguide transition probe will be replacedwi th a broadband probe. The uni t wi11 then be matched, tes ted, andreturned to Rosman for installation. No changes will be made to thebearings, bearing housings, or any external dimensions ~ therefore, therotary joint can be easily replaced in the system without any considerationfor mechanical and electrical interface.

In preparing for these modifications, an RF model of the phase­compensating rotary joint has ,been built and tested. Measured data onthis model (Figure 16) shows that an axial ratio of less than 1.5 dBcan be realized over the entire receive band from 3.7 to 4.2 GHz. Furthereffort will be directed toward improving the axial ratio to less than1.0 dB and providing an impedance match better than 1.5:1 over the band.

Once performance of the RF model is found to be acceptable, a set ofmodification drawings will be prepared and detailed parts will befabricated. These drawings and parts will then be set aside until theRosman rotary joints are returned to Orlando for modification.

3.1.1.3.5 Mechanical Configuration

The feed cone design locates the "antenna-mounted unit" portion ofthe parametric amplifier in the approximate position of the presentParamp. The new OMT, diplexer, and transmit-reject filters are alsolocated in approximately the same position as the existing units. Spacehas also been allocated for future installation of a 6-inch-long cross­guide coupler for the millimeter wave noise source between the diplexer,transmit-reject filter, and the antenna-mounted portion of the parametricamplifier. Provisions have also been made for installing two flexible

28

3.0

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waveguides 4 inches long (for strain relief) in each waveguide runadjacent to the transmit-reject filters. The two band-pass filters(614-01511) will be mounted near the existing monopulse comparator inthe top of the feed cone. The tracking down-converter (614-01526) willbe located in the position presently occupied by the monopulse converter.Since final dimensions of the OMT are not now available, a detailedlayout of the Rosman feed cone assembly is not included in this report.

3.1.2 Mojave/TGS 40-Foot Antenna

A block diagram of the equipment configuration to be employed in theMojave and Transportable Ground Station (TGS) feed cones is shown inFigure 17. Essential features include:

1 A feed system comprised of polyrod antenna elements

2 A center polyrod used expressly for transmitting up to 16 kW CW

3 A four-element array of polyrods for monopulse tracking, receivingcommunication signals, and polarization sensing

4 Capability to transmit parallel or perpendicular to the receivedsignal

5 Low-noise, cooled amplifier

6 Filters to isolate the transmitter from the receiver

7 Automatic polarization alignment.

Operation of the modified feed and microwave network for the Mojaveinstallation is essentially the same as the present system, except forthe increased frequency range covered by the new system. The configura­tion of the feed network will remain unchanged. Transmit reject filterswill be provided to cover the new frequency band. The existing directionalOQupler in the communication channel will be retained and calibrated overthe new frequency band. New coaxial couplers will be provided in thePolang and tracking error channels. The test switching circuits used toinject noise and CW signals into the low-noise amplifier will be thesame as the test signal circuits at Rosman.

The existing Transportable Ground Station (TGS) system employs apseudo-monopulse tracking system wherein the communications signals, thesum, 6EL and 6Az tracking signals, and the 6Polang signals are routeddown a common line through a common low noise amplifier. Angle trackingand Polang tracking functions are performed by time sharing a singletracking receiver. The key element to this system was the time division.multiplexer (lobing switch) which sequentially samples the 6EL, 6Az,and ~ Polang signals.

The TGS system is being modified to make the tracking system identicalto Mojave, i.e., a three-channel monopulse system. NASA will provide twoadditional tracking receivers to implement this change. In layout, the

30

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TGS system is exactly like Mojave. The feed/comparator assemblies areidentical and will require similar modification to render it usable downto 3.7 GHz. The 6 Polang hybrid and the three couplers are new unitssince they do not currently exist on the TGS system. Other than theseitems, the new units to be supplied and the units to be modified areidentical to Mojave.

3.1.2.1 Feed/Comparator Assembly

The feed/comparator assembly is composed of po1yrods, po1arizers,orthomode transducers, adapter/phasing plate, and comparator network.The complete assembly was initially designed to receive at 4.05 to 4.2GHz and transmit at 5.9 to 6.4 GHz. Measured data distributed at theBidders' Conference of 1969 showed that the feed/comparator assembly,as installed in the 40-foot reflector, degrades in receive band perfor­mance below 4.0 GHz. The TGS feed/comparator assembly was removed byMartin Marietta and brought to Orlando for inspection and measurement.Assembly measurements confirmed the NASA data, indicating a noticeablechange in performance below the design band. The feed was then dis­assembled into the smaller subassemblies for more complete and thoroughmeasurement, which demonstrated that every subassembly falls short ofthe desired performance below 4.0 GHz.

with the exception of the po1yrods, each subassembly has beenredesigned to extend its measured performance from 4.0 to 4.2 GHz overthe entire frequency band from 3.7 to 4.2 GHz. Some modifications arenow complete, while some have recently been released to drafting fordetailed drawings. There is no indication that performance will be com­promised in extending the operating frequency band of existing hardware.The next critical milestone, then, is testing the complete modified feed/comparator assembly.

The object of the feed modification program is to make the "fullband" performance of each subassembly equal to, or better than, thein-band (4.0 to 4.2 GHz) performance of that subassembly prior to modifi­cation. In this way, satisfactory performance of the complete feed/comparator network can be ensured (with only minor adjustments) when thesubassemblies are recombined. To follow this plan, it was necessary tomeasure and record the complete performance of each original subassemblyto provide a baseline for evaluating the modification progress andperformance. Data from the Sylvania Final Report* was used as a guidefor evaluating the validity of Martin Marietta data. In most cases, datafrom Sylvania compared closely with that from Martin Marietta; in a fewcases, however, deviations were considered to be significant. A consider­able effort was directed toward resolving these differences through changesin equipment, setups, and even personnel. In a few cases (in particular,measurements of insertion loss), it was necessary to proceed with modifi­cations in spite of the difference. The Martin Marietta measurements willserve as baseline data, then, for future evaluation of the subassemblymodification program.

* Sylvania Final Report F178-l, Contract NAS5-9533, "ATS TransportableCommunications Ground Station," Sylvania Electronics Systems, November1964-1966.

32

Current modifications involve only the TGS assembly; drawings andplans, however, are directly applicable to the Moj ave assembly. Further­more, double quantities of all new parts and components have already beenfabricated and are awaiting return of the Mojave feed to Orlando formodification. The Mojave feed/comparator subassembly will be removed andreturned to Orlando as soon as the Antenna Pre-Mod Test Program is completed.

3.1.2.2.1 Antenna Elements (Polyrod)

Such transmitting antenna elements and associated system componentsas the polarizer, chokes, and transitions perform well down to 5.9 GHz,according to Sylvania, and will be retained in their present form. Carewill be taken not to change their characteristics as a result of any othermodifications. (Martin Marietta measurements showed a maximum VSWR of1.5:1 at 6.0 GHz whereas Sylvania reported a maximum of 1.3:1 at the samefrequency. This difference is most likely occasioned by a partially burnedpressure window found in the feed when it was removed from TGS at Mojave.)

The receiver elements are 17-inch-long, tapered teflon rods externalto the 2-inch I.D. circular waveguide. Element parameters were initiallydesigned by Sylvania to cover the 3.8 to 4.4 GHz band. An inter-elementspacing of 4.5 inches (1.6A at 4.2 GHz) was determined to be optimum forthis initial band. Extending the band downward to 3.7 GHz with an upperband edge of 4.2 GHz represents a decrease in required bandwidth over theinitial design. Retaining the present 4.5-inch element spacing permitsthe polarizer gearbox casting, drive motors, synchros, etc. to be reused.This represents a significant advantage. With regard to array performance,the fact that the frequency extension is in the lower direction is anadvantage. The initial 4.5-inch spacing was the closest that could beattained and still allow room for the transmitting element and associateddrive gears. Lowering the frequency is equivalent to moving the elementscloser together. The characteristics of that portion of the differencepattern incident on the subreflector are so slightly changed that nomeasurable difference in tracking performance is anticipated. MartinMarietta-measured VSWR data (Figure 18) indicates very good performanceover the band from 3.7 to 4.2 GHz. No modifications to the polyrod ele­ments will be required.

3.1.2.2.2 Half-Wave Polarizer

The nonlinearity evident at frequencies below 3.9 GHz in Polanqsystem data made available at the Bidders' Conference is due to phasedispersion between orthogonal components in the half-wave polarizers.If these polarizers were modified to have a differential phase shift of180 degrees with close tolerance and equal characteristics down to 3.7GHz, tracking linearity would be satisfactory.

Prior to embarking on modification of the polarizers, a series ofbaseline tests was conducted in the anechoic chamber to evaluate performanceof the polarizers without the influence of the 40-foot reflector. Tomake these measurements in the controlled environment of the anechoic

33

1.

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1\ ,.. J ,V\ \ V\ v

1 / 1\/\I) ~\ \v V \ I \ I \ I

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3.7 GHz 4.2 GHz

Figure 18. VSWR of Receiver Polyrods

34

chamber, the feed wiring was so altered that the polarizer drive motoraccepted commands from the pattern recorder console and the polarizersynchro drove the chart paper as well as the position indicator of therecorder. This instrumentation made it possible to measure and recordthe axial ratio of each polarizer through the polyrod antennas.

The most significant measurements were a series of null position andnull depth recordings as a function of frequency. A coax-to-waveguideadapter with detector was placed on the Polang port of one GMT, thetransmit polarization was selected to be aligned with the Polang portpolarization, and the feed polarizer section was slowly rotated. Underthese conditions, it is the action of the lBO-degree polarizer sectionthat produces a null when the pins are aligned at 45 degrees to theincoming polarization. The effectiveness of the polarizer pins can bedetermined by the null depth. By re-running the null position measure­ments for each frequency in the band from 3.7 to 4.2 GHz, the frequencydependence and effectiveness of the polarizer can be determined.

Measured data is presented in the superimposed pattern of Figure 19.From this, it can be seen that there is a considerable null error at3.7 GHz which must be corrected to meet the Polang tracking linearityspecification of 2.0 degrees.

A breadboard model of a polarizer section (Figure 20) was fabricatedto electrically reproduce the actual units in the feed, e.g., same I.D.,length, and pin spacing. Pin depth and the number of pins were designedto be variable. A special fixture (Figure 20) was designed and fabricatedto assist in the design and testing of the polarizer. This fixture iscomposed of a transition from WR229 to 2-inch circular waveguide on eachend of the breadboard polarizer, which is inserted between two pillow blocksof the fixture. This fixture permits the selection of input and outputpolarization while allowing the polarizer section to be rotated continuouslywith respect to both transitions. This fixture closely approximates thepolarized mechanisms in the feed.

The depth and number of pins were errq:>irically determined with theaid of the swept-frequency insertion-loss display on the Hewlett-Packardmi crowave network analyzer. It was found that the addition of a seventhpair of pins made a significant irrq:>rovernent in the broadband performance·of the polarizer. Performance of the final breadboard polarizer, corrq:>aredto the unIrodified TGS polarizer, is summari,zed below.

Null Depth and position

The breadboard test fixture was designed to accept a single TGSpolarizer as well as the breadboard model in order to test both unitson an equal basis. Again, with the input and output polarization ~ligned,

each polarizer was rotated for minimum signal, which should occur at 45degrees pin orientation. The data contained in Table 5 shows that theexisting TGS polarizer has a maximum null shift of 10 degrees, while thebreadboard polarizer has only 1.8 degrees (maximum) shift over the entire

35

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Figure 19. Measurements of Axial Ratio Null Depth and position Versus

Frequency (TGS Feed)

36

-

Figure 20. Breadboard Polarizer in Test Fixture

....

....

-

TABLE 5

Polarizer Null Position Stability

TGS Polarizer Breadboard PolarizerFrequency 6 Pins - Unmodi fied 7 Pins(GHz) (dearees) (deqrees)

3.7 -8.1 -0.4

3.8 +3.0 +0.3

3.9 +0.9 +0.9

4.0 0.0 +0.9

4.1 0.0 0.0

4.2 0.0 0.0

37

band from 3.7 to 4.2 GHz.

Insertion Loss

In comparing insertion loss data from the breadboard and the existingpolarizer (Figure 21) there is on the average very little difference.except in the vicinity of 3.7 GHz where the breadboard model shows aconsiderable improvement, from >5.0 dB to only 0.25 dB. (This dataincludes losses of the rectangular-to-circular waveguide transitionswhich are part of the measurement fixture.) The sharp resonances recordedon the existing unit have been verified. Although the cause is not fullyunderstood, similar resonances which were evident in the breadboard modelwere tuned out by adjusting pin depth.

The breadboard polarizer design is currently being detailed anda step-by-step plan for implementing this design in the existing unitis being developed. The TGS feed is completely disassembled and thepolarizers will be modified as soon as the drawings are released. Eachpolarizer will be individually optimized and matched using the specialbreadboard fixture. When all tests are complete, the new units will beinstalled in the feed and the assembly will be rebuilt.

3.1.2.2.3 Orthogonal Mode Transducer (OMT)

The OMT used here consists of an in-line circular waveguide with anorthogonal rectangular waveguide (WR 229). One end of the circular guidemates wi th the choke joint and half-wave polarizer. The other end iscoupled to rectangular waveguide through two Xg/4 transformer sections.various matching devices are used at the three ports.

VSWR, insertion loss, and isolation performance of the OMT's reportedby Sylvania are excellent over the 3.98 to 4.225 GHz band, with VSWR'stypically being lower than 1.06 and isolation of 38 dB Qr qreater. Theinitial swept-frequency measurements made at Martin Marietta and reportedin the Design Review Report, OR 11,239, indicated that OMT performancewas acceptable. Since then, additional measurements showed a sharp reson­ance in VSWR and insertion loss in the vicinity of 3.7 GHz (Figure 22).It was also found that the thin septum, which is added to decrease cut­off (waveguide width), is the cause of this resonance. Measurements madeon a breadboard model of the OMT displayed an almost identical resonance.Preliminary experimentation indicates this resonance can be eliminated bychanging the length of the septum contained in the through port. Thisdesign will continue until the resonance is completely eliminated.

3.1.2.2.4 Adapter/Phasing Block

The adapter block mates the input ports of the comparator to the in­line ports of the orthomode transducer. Broached holes in the block areat a diagonal angle in the' H-plane and were cut )..,g/2 (4.0 to 4.2 GHz)in length to minimize mismatch. Each waveguide section in this blockcontains a pair of screws spaced Xg/4 apart for phase trimming.

38

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Figure 21. Insertion Loss Comparison of UnmodifiedTGS Polarizer and Breadboard Polarizer

39

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40

The only modifications contemplated for this component are retuning ofthe phase-compensating screws to balance the feed/comparator assembly.

3.1.2.2.5 Monopulse Comparator

The monopulse comparator was fabricated from two basic hybrid types:the folded H~plane tee and a standard magic tee. Two MOL Model 229TH12 folded H-plane hybrids were used in fabricating the comparatorassembly. According to MOL, these devices were designed and tested tooperate over the 3.7 to 4.2 GHz band.

The complete comparator package was made as compact as possibleto minimize line lengths and, consequently, losses. Figure 23 showsthis assembly. To accomplish such a compact design, the E-plane matchingstructure of the MOL unit was completely removed and rematched as a combinedjunction with the center magic tee. Eccentric posts were employed atseveral junctions to obtain final matching and to optimize the balancebetween ports. It was found that inductive irises inserted near theantenna input ports were needed for adequate balance. These matchingstructures were far from the reflection source, resulting in reducedbandwidth. Narrow-band performance in the assembly, however, was superiorto the individual MOL hybrids as they were received from the vendor.

Swept-frequency measurements made at Martin Marietta verified superiorin-band performance (4.0 to 4.2 GHz) and showed that performance in theband from 3.7 to 4.0 GHz is unusable as the VSWR and insertion loss arenot consistent with requirements. Insertion loss (4.0 to 4.2 GHz) wasnominally 0.25 dB as measured between the sum output port and one of thefour antenna ports (Figure 24). According to data published in Sylvania'sfinal report, the insertion loss should be less than 0.007 dB. Therefore,several measurement techniques and equipment variations were employed toresolve the difference in data, only to find excellent correlation of allMartin Marietta data. It is obvious from the swept insertion-loss data(Figure 24) that, at certain frequencies, insertion loss is very low.Discrete frequency tests of these low-loss points, using the AIL Attenua­tion Calibration Model 137, show good correlation with Sylvania data. Acontinuing effort is being made toward resolving the differences in measureddata; however, the comparators have been redesigned and are currently beingtested against Martin Marietta baseline data.

NASA made a spare comparator available to Martin Marietta for addi­tional measurements and for use as a breadboard for designing and imple­menting trial fixes for test and evaluation. Tests were also run on thespare unit prior to its modification. Results of the modification canbest be described by comparing before and after data as follows:

VSWR

The pre-mod data (Figure 25) shows a serious increase in the sumand elevation error VSWR below 4.0 GHz. Post-mod data shows the successachieved in rematching the comparator network. The matching procedure

41

SUMOUTPUT

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Figure 23. Monopulse Comparator

42

ANTENNAELEMENTINPUTS

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I I I I I I*MEASURED WITH "13]'1 ATTENUATOR CALIBRATOR

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Figure 24. Insertion Loss Measurements of TGS Comparator (Unmodified)- Sum Port to Antenna Port

43

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The improved comparator was then completely tested to ensure that noother parameters were adversely affected. For example, the VSWR of thecomparator looking into each of the feed ports (Figure 27) shows thatthe pre-mod performance was also improved over the extended band.

Insertion Loss

A comparison of post-mod insertion loss data (Figure 2B) withpre-mod data (Figure 25) shows definite improvement in the vicinity of3.7 GHz with no noticeable change in the 4.0 to 4.2 GHz band. Thedifference in flatness of the swept calibration points between pre- andpost-mod data is due to the use of different equipment and in no wayreflects a change in performance.

Isolation

The most important isolation measurements (Figure 29) between thesum and two error ports shows a minimum isolation of 35 dB over the band,which is more than adequate.

Phase Balance

The phase balance, measured with the Hewlett-Packard MicrowaveNetwork Analyzer, reflects the relative phase response at each of the fourantenna ports to a signal entering the comparator in the sum and two errorports. Ideally, the sum port insertion should produce an in-phase responseat each of the antenna ports, while an insertion at either of the two errorports would produce a lBO-degree phase shift in two of the antenna portsrelative to the other two. Table 6 tabulates the measured data andincludes the phase-shifting mechanism of the adapter blocks, which wasadjusted only for the unmodified comparator. Although it is not possibleto make a direct data comparison, it is obvious that the modified unit isequal to, or better than, the original.

3.1.2.3 Band-Reject Filters

A band-reject filter is required in the communications receivechannel at Mojave to meet the specification requirement of 100 dB minimumisolation between transmit and receive signals. A minimum of 40 dBis realized by use of separate transmit and receive elements; thus, thefilter must supply 60 dB minimum in the new system.

Existing units do not provide sufficient transmit band rejection inthe extended band and cannot be used in the modified system. A specifica­tion has been written to cover the requirements of a filter to operate

45

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Figure 28. Post-Modification Insertion Loss Measurements of Spare Comparator ­Sum Port to Antenna Port

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SUM RFI WGPRE-POST-COAX.....--HYBRID~CHANNEL ~OMI"I---DIPLEXERI---

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DOWN-CONVERTER~

COUPLERCOAXHYBRIDTORECEIVER RELAY

-14TO-50(RO

lJ1OJ

Figure35.Rosman-Mojave-TGSCommunicationsChannels

DIPLEXERPHASECONNECTINGDOWN-CABLEOMI"~&TRFILTER

~COMPENSATING~CABLEI--TDA~CONVERTERI--TOTRACKING

ROTARYJOINTRG214RECEIVER

Figure36.PolarizationError-TrackingChannel

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3.2.1.3 Angle Tracking Channels

Figure 37 is the updated, simplified block diagram for theangle tracking channels. Again, the model takes into account updatedgain or loss figures for the filters and adds the cable loss previouslyomitted. Table 9, which presents the net results for each site,corresponds to Table· XVI, page 65, of the Design Review Report.

foIlNOPULSECOMPARATOR

BAND PASSFILTER

CABLERG 214

DOWN­CONVERTER

CABLETO

TRACKING RCVR

Figure 37. ~X and ~y Error Channels

TABLE 9

Angle Tracking-Error Channels

Rosman Mojave TGS

Gain Noise Temp. Gain Noise Temp. Gain Noise Temp.Component (dB) Contribution (OK) (dB) Contribution (OK) (dB) Contribution (OK)

Cable -0.16 10.5 -0.40 25.0 -0.24 15.5

Bandpass Fi1te -0.35 23.0 -0.35 23.0 -0.35 23.0

Test Coupler -0.3 19.0 -0.3 19.0 -0.3 19.0

Cable -1.12 66.0 -0.8 49.0 -.64 40.0

Down-Converter +28.2 5500.0 +28.2 5500.0 +28.2 5500.0

Cable r-15.0 22.0 -7.0 3.0 -4.0 1.1

TOTAL 13.2 5640.5 +21.2 5619.0 +24.2 5598.6..

(Ref. to (Nf=13.1dB) (NF=13.0dB) (NF=13.0dB)Down-ConverterInput)

61

3.2.2 Cooled Parametric Amplifier

The antenna-mounted unit portion of the parametric amplifier isshown in Figure 38. At e~ch site, this unit, along with the universalpower supply, is mounted within the feed cone area. At the Mojave sitethe local amplifier control unit and local .refrigerator control unit arenon-pressurized, rack-mounted, and are located in the feed cone area forweather protection (Figure 31). The remote amplifier control units arealso rack-mounted units and will be located in the instrumentation andoperations buildings at Rosman and Mojave respectively and in the oper­ations trailer (V-IO) at the TGS site. The compressor units are self­contained units floor mounted at the base of the antenna at each site.

The cooled parametric amplifier is composed of three varactor stagesmounted in a vacuum dewar on a helium refrigerator cold station at20 degrees K. A controlled, solid state Gunn diode oscillator (~30 GHz)is employed as the pump source for the three stages of parametricamplification. Following the last varactor diode stage is a transistoramplifier mounted outside the dewar on the electronic chassis alongwith the Gunn diode pump source and its amplitude control circuits.Significant technical characteristics of the amplifier are:

Gain:

Noise temperature:

Bandwidth:

Ripple:

Gain Slope:

VSWR:

1 dB compression point:

Delay distortion:

Intermodulation:

60 dB minimum

17.5°K maximum at input WG switch flange

500 MHz at the 1 dB points

+0.75 dB maximum

0.4 dB/MHZ in any 20 MHz

1.35:1 (input); 1.3:1 (output)

In-band -50 dBm: transmit band +30 dBm

Linear, 0.3 nsec/40 MHz;parabolic, 0.025 nsec/MHz2 ;ripple, 0.3 nsec peak to peak

Less than -45 dBm at the output withtwo in-band signals at a level of -60 dBmand another signal in the transmit bandat a level of -30 dBm.

62

FLAP A"TT£.NlJATOR

POW':'R~~:) CONTROLCONN£.CTORS

.~.

lliCTRONIrc.----~

E.NCLOSUR£.

COLD LOAD ---~/WAVEGUID£.

VACUUM

INP~T WAVEGUIDE.

HELIUM LlNE.S --_.

COA'A AD"PTER

o

~BLDWER H~DROGEN VAPOR-PRE.SSUREGUAGE

Figure 38. Antenna-Mounted Unit Portion of Parametric Amplifier

63

The cooled parametric amplifier also contains a built-in cold load,attenuator card (flap attenuator),and waveguide switches. The built-incold load is physically attached to the 20 degree K cold station and canbe applied to the input of the cooled paramp by remote control of thewaveguide switches. The flap attenuator can be operated only locally,at the paramp, for the Y factor measurement. There is, however, a solidstate noise source (AIL Model 76) whose output is calibrated and can beapplied to the paramp input by remote control; thus, the Y factor can bemeasured by the operator in the instrumentation room.

In addition to the hot and cold loads, a linear receiver with precisegain control must be employed to measure the Y factor. This linearreceiver is made up of one of the communication down-converters whichfollows the cooled paramp whose 70 MHz output is located at the patchpanel in the instrumentation room. The output is then applied to theinput of a test receiver such as the AIL Type 136 receiver, which hasan IF attenuator whose accuracy is better than ~0.05 dB. The receiver­detected output is then displayed on a mirrored panel meter.

The operator switches-in the built-in cold load and adjusts the IFattenuator for half scale reading on the panel meter. The IF attenuatorsetting is recorded; the ou~put of the calibrated solid state noise(hot load) is then switched-in, and the IF attenuator is adjusted toobtain the same half scale reading on the panel meter. The IF attenuatorsetting is then recorded; the difference between the two attenuatorrecordings is the Y factor in decibels. The cooled paramp noise tempera­ture can now be determined by the formula:

T paramp = T YThot load - cold load

Y-l

where Y is expressed as a power ratio, and the temperatures are in degreesKelvin.

To make the measurement with a ~l degree K accuracy, the hot/cold loadtemperature must be known to within ~3 percent, assuming a hot load tempera­ture of 300 degrees K and a cold load temperature of 30 degrees K.

64

3.2.3 Communication Down-Converter

Basic dimensions of the overall communications down-converter packaqeare 13.25 inches wide, 7.13 inches high, and 12.00 inches deep (Figure 39).At each site, the unit is mounted in standard 19-inch racks; additionalbracketry required for mounting is currently being designed. The unitwill be sealed and will have provisions for pressurization.

Two identical units at each site will employ double conversion withlow side local oscillator injection. The first IF is 880 MHz and thesecond IF is 70 MHz. Any input frequency within the range of 3.7 to 4.2GHz can be remotely selected by means of a John Fluke (645A or 6160A)synthesizer located in the instrumentation room. Major technical character­istics are:

Input frequency

Input impedance:

Input level range:

Noise figure:

Overall gain:

Amplitude flatness:

Group delay:

3.7 to 4.2 GHz

50 ohms with a VSWR of 1.2:1 maximum

-13 to -103 dBm

22 dB maximum

15 dB maximum with 10 dB adjustment

+0.2 dB/40 MHz bandwidth

Linear - 0.1 nsec/MHz2.0 nsec/40 MHz

2Parabolic - 0.025 nsec/MHz

Ripple - 1.0 nsec peak to peak

Intermodulation products: 50 dB below either output signal levelwhen their input levels are -15 dBmmaximum

output center frequency:

output Bandwidth:

output impedance:

output spurious:

output signal to singlesideband phase noise:(measured in a 1 Hz band­bandwidth)(Refer to 614-01525,page llA)

70 MHz

50 MHz at the 1 dB bandwidth

75 ohms with a VSWR of 1.1:1 maximum

63 dB below the desired output signal

57 dB at 10 Hz from the carrier, fallingoff at the rate of 10 dB per decade to10 kHz away from the carrier. At 1 MHzfrom carrier, it will be at least 100 dB.

65

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Figure 39. Communications Down-Converter Configuration

66

The above specifications will apply when the first local oscillatoris derived from a Fluke 6160A synthesizer and the second local oscillatoris derived from a Martin Marietta 90 MHz signal phaselocked to the stationstandard.

The communications down-converter (Figure 40) employs a circulator atthe input to ensure a 1.2:1-VSWR, 50-ohm input. This circulator alsohelps terminate one end of the bandpass filter, which keeps the amplitudeand delay ripples to a minimum. The bandpass filter passes the desiredsignal while attenuating the image, first local oscillator, and trans­mitter frequencies. The first mixer converts the input signal to 880 MHzand is then applied to the bandpass filter. The filter attenuates theundesired products of the first mixer, as well as image frequenciesassociated with the second mixer. A circulator terminates the bandpassfilter and presents a good driving impedance for the second mixer, thusminimizing the amplitude and delay ripple. The second mixer convertsthe 880 MHz signal to 70 MHz and is followed by a low-noise, variable­gain preamplifier with a 7S-ohm output impedance.

The "x72" frequency mUltiplier utilizes a configuration of x2x3x3x4.This will provide a sufficient percentage frequency separation betweenundesired sidebands at the output of each multiplier stage to permiteffective filtering.

All components for each communication down-converter are mounted ina pressurized container and are interconnected with solid 50-ohm coax andSMA connectors. The panel connector for the RF input is a precision "N"and the output connector is a 7S-ohm TNC. All other RF panel connectorsare Type "N". The down-converter operates from the +28 VDC of power supplyassembly 614-01610. This input power is filtered and regulated down to+20 VDC for the "x72 multiplier and the 70 MHz preamplifier.

67

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3.2.4 "X9" Multiplier

Basic dimensions of the overall "x9" multiplier package are 13.25inches wiqe, 7.13 inches high, and 12.00 inches deep (Figure 41). Ateach site, the unit is mounted in standard 19-inch racks; additionalbracketry required for mounting is currently being designed. The unitwill be sealed and will have provisions for pressurization.

The "x9" frequency multiplier (MM Specification No. 614-01518-A) isshown in block diagram form in Figure 41. A single unit furnishessecond LO power to both communications down-converters at each site.Its electrical characteristics are:

output frequency:Output power (each output):Output VSWR:Spurious output:Output port-to-port isolation:

Input frequency:Input power:Input VSWR:

810 MHz+10 dBm +1 dB1.5: 1 maximum80 dB minimum below the output60 dB minimum over the range

of 50 MHz to 1 GHz90 MHz+6 dBm +3 dB2:1 maximum

The "x9" frequency multiplier components are mounted inside a separatepressurized container that has Type "N" panel connectors for the RF signals.Interconnecting cables within the container are solid 50-ohm coax with SMAconnectors.

3.2.5 Tracking Down-Converter

Basic dimensions of the overall tracking down-converter package are17.00 inches wide, 9.00 inches high, and 14.20 inches deep (Figure 42).At each site the unit is mounted in standard 19-inch racks; additionalbracketry required for mounting is currently being designed. The unit willbe sealed and will have provisions for pressurization.

The tracking down-converter has four channels (61 ,6 2 , 6pOL ' I), eachemploying double conversion with low side local oscillator injection. Thefirst IF is 880 MHz and the output frequency is 136 MHz. Any input frequencywithin the range of 3.7 to 4.2 GHz can be remotely selected for all fourchannels simultaneously by a Fluke synthesizer located in the instrumen­tation room. The necessary multiplier for the first local oscillator iscontained within the down-converter assembly as is a crystal oscillatorand multiplier for the second local oscillator.

69

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71

MAJOR TECHNICAL CHARACTERISTICS

Input frequency range:

Input impedance:

rnput level range:

Noise figure:

Channel-to-channel isolation:

Overall gain: L:,l, L:,2

L:,POL

E

Amplitude flatness:

Intermodulation products:

output center frequency:

Output bandwidth:

Output impedance:

Output spurious:

Local oscillator stability:

72

3.7 to 4.2 GHz

50 ohms with 1.5:1 VSWR

L:,l' L:, 2 -51 to -141 dBm

L:,POL -31 to -121 dBm

I -21 to -Ill dBm

L:,l' L:,2 13 dBm maximum

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I 21 dB maximum

60 dB minimum

28.2 dB/+2, -8 dB gain control

13.2 dB/+2, -8 dB gain control

13.2 dB/+2, -8 dB gain control

+1.0 dB peak to peak

60 dB below either output signallevel when their input levelsare -20 dBm

136 MHz

3.0 MHz at the 3 dB points

50 ohms

Due to transmitter leakageand first local oscillatorproducts (fifth order), 33 dBminimum below the desiredsignal. Due to first andsecond local oscillator products(fifth order), 34 dB minimum

below the desired signal. Allother spurious, 60 dB minimumbelow the desired signal.

Long term, +5 parts in 109/day ;short term,-l x 10-10 rms/lsecond average.

The above specifications applywhen the first local oscillatoris derived from a Fluke synthe­sizer and the second local oscil­lator is derived from an ultrastable 9.1851852 MHz crystal oscil­lator.

The tracking down converters (Figure 43) employ identical inputbandpass filters (3.7 to 4.2 GHz) as the communications down-converter.This bandpass filter passes the desired signal while attenuating theimage, first local oscillator, and the transmitter frequencies. Thecir~ulator following the filter terminates the filter and the mixer fora broad band of frequencies other than the passband. The first mixerconverts the input frequency to 880 MHz, and, in the ~l and ~2 channels,its output is applied to an 880-MHz amplifier. The ~POL channel has atunnel diode amplifier while the [ channel has the cooled parametricamplifier ahead of their tracking down-converters. Thus, any additionalgain provided by an 880-MHz amplifier is not required.

The 880-MHz bandpass filter attenuates the undesired first mixerproducts and image frequencies associated with the second mixer. Thecirculator following the bandpass filter presents a stable broadbandimpedance for the second mixer. The second mixer converts the 88o-MHzsignal to 136 MHz and is followed by a variable-gain preamplifier with a50-ohm output impedance.

The local oscillator chain, associated with the first mixer, acceptsthe output of the Fluke synthesizer (located in the instrumentation room)and multiplies its output frequency by 72 (the order of multiplication isx2x3x3x4). After the second "x3," there is a high-level (approximately+30 dBm) 80o-MHz signal generated which is the input to the "x4" diodemultiplier (last stage) and four-way power divider. Power and signallines must be well shielded to keep this high level signal from leaking intothe first IF (880 MHz) amplifier. The 16 percent bandwidth of the multi­plier chain allows complete tuning of the entire tracking down-converterto be accomplished by changing only the output frequency of the Flukesynthesizer.

The second local oscillator is derived from a fixed-frequency crystaloscillator. This oscillator is followed by a crystal filter which atten­uates the noise sidebands by 60 dB. This filter prevents the higher levelnoise sidebands from mixing, in the multiplication process, and fallingnear or on top of the main signal which degrades frequency stability.output of the crystal filter is applied to a "x8l" frequency multiplier,and the order of multiplicatior. is x9x9.

All components for all four channels are mounted in a pressurizedbox and are interconnected with solid So--ohm coax and SMA connectors.panel connectors for all RF signals are Type "N." Tracking down- converterpower is +28 VDC which is supplied by the power supply assembly (614-01610).The 28-VDC input is filtered and regulated down to +20 VDC.

73

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3.2.6 Performance Monitor/Frequency Translator

Basic dimensions of the overall Performance Monitor/FrequencyTranslator (PM/FT) package are 17 inches wide, 9 inches high, and 14.20inches deep (Figure 44). At each site the unit is mounted in standard19-inch racks; therefore, additional bracketry required for mounting iscurrently being designed. The unit will be sealed and have provisions forpressurization.

The PM/FT unit includes two independent test tools, only one of whichcan operate at one time. A block diagram is shown in Figure 45.

The frequency translator accepts a sample of the C-band transmitteroutput (modulated or unmodulated) and translates it downward to the inputfrequency range of the C-band receiver. The desired receive frequency isalso set by employing the frequency synthesizer* mentioned above. In thecase of the Frequency Translator (FT), however, only certain combinationsof transmit and receive frequencies may be used. These combinations includenearly all of the expected ATS-F uplink and downlink frequencies (Table10). For those combinations which have spurious responses in excess ofdesired levels, a non-ATS-F receive frequency can always be found whichwill avoid the problem.

The Performance Monitor (PM) accepts a 70-MHz signal (which mayhave any modulation up to a 40-MHz bandwidth) and translates it upwardto any desired frequency within the receive band of 3.7 to 4.2 GHz. Theexact frequency is determined by use of a Fluke synthesizer located in theinstrumentation room. Output of the PM may be applied to the input of thereceiver cooled amplifier. Thus the entire receiver subsystem may beevaluated with a modulated signal.

Detailed descriptions of the two functions follow.

3.2.6.1 Frequency Translator

Figure 46 shows the frequency translator in block diagram form.The signal path consists of a simple mixer which translates the transmittersignal to the receive frequencies. Local oscillator (LO) for the translatoris derived from a self-contained multiplier subsystem which generates (La)frequencies in the range of 1.7 to 2.7 GHz, under control of a synthesizerin the instrumentation room.

The multiplier subsystem consists of a common x2x2x2 section whichdrives anyone of four additional mUltipliers. This arrangement isnecessary due to the wide percentage bandwidth represented by the 1.7 to2.7 GHz output, which would make it difficult if not impossible to achievesuch bandwidth in a single unit.

*In accordance with Contract Amendment 1 and NASA Synthesizer Plan dated11 August 1971, use of the Frequency Translator/Performance Monitor isconsidered an "off-line" function and a dedicated synthesizer is not pro­vided for its use. Synthesizers may be diverted from other receiver (or.other system) functions for this purpose.

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77

TABLE 10

Frequency Translator LO Frequencies and Second Harmonics, andSeparation of Such Harmonics from Desired "Receive" Frequencies

Transmitter Separation ofFrequency Rec.Freq. LO Freq. 2 x LO Freq. Center Frequencies

(MHz) (MHZ) (MHZ) (MHz) (MHz)

4119.599 2092.495 4184.990 65.391

4178.591 2033.503 4067.006 102.585

6212.094 3750.000 2462.094 4924.188 1174.188

3950.000 2262.094 4524.188 574.188

4150.000 2062.094 4124.188 25.812 *

4119.599 2181. 451 4362.902 243.303

4178.591 2122.459 4244.918 66.327

6301. 050 3750.000 2551. 050 5102.100 1352.100

3950.000 2351.050 4702.100 752.100

4150.000 2151. 050 4302.100 152.100

4119.599 1830.401 3660.802 458.797

4178.591 1771. 409 3542.818 635.773

5950.000 3750.000 2200.000 4400.000 650.000

3950.000 2000.000 4000.000 50.000 *

4150.000 1800.000 3600.000 550.000

4119.599 2030.401 4060.802 58.797

4178.591 1971. 409 3942.818 235.773

6150.000 3750.000 2400.000 4800.000 1050.000

3950.000 2200.000 4400.000 450.000

4150.000 2000.000 4000.000 150.000

4119.599 2230.401 4460.802 341. 203

4178.591 2171. 409 4342.818 164.227

6350.000 3750.000 2600.000 5200.000 1450.000

3950.000 2400.000 4800.000 850.000

4150.000 2200.000 4400.000 250.000

*These combinations (and difference frequencies between Second Harmonic anddesired frequency) will provide marginal signa1-to-spurious performance.

78

Selection of the mUltiplier, and of the synthesizer setting to beemployed to achieve the desired translation, must be determined by theoperator by calculation and by operation of selection switches at thecontrol and monitor panel.

It is readily seen that the second harmonics of LO frequencies from1.85 to 2.1 GHz fall in the receive band of 3.7 to 4.2 GHz. Furthermore,although this spurious response represents an even-order product thatwill be suppressed favorably by the doubly balanced mixer, a 40 dB rejec­tion is about the best that can be achieved. Achieving an LO level of+10 dBm (a desirable level for other reasons), the output of the mixerwould contain undesired signals at approximately -30 dBm. Optimizing inputsignal levels will result in desired signals at the output of the mixerof about -17 dBm at the highest expected input level. Thus signal-to­spurious ratios of no better than 23 dB could result. With lower levelinputs, this ratio could be degraded linearly. Adjustment of input padsand LO levels may improve this somewhat, but cannot be expected to producethe desired signal-to-spurious ratios for all frequency translation combi­nations.

An alternative to this method of operation was proposed by Aertech,the subcontractor producing this subsystem. The alternative could involveusing the transmitter sample signal as the LO source, with the multiplieroutputs being adjusted to a much lower level (in the area of -20 to -40dBm). At these levels the production of an undesired second harmonic wouldbe greatly reduced, achieving a desirable spurious response in the order of60 dB below the desired signal. To implement this, the transmitter samplesignal would have to be in the order of +30 dBm with an ALe loop normalizingit to approximately +10 dBm at the input to the mixer.

NASA-GSFC has directed that this approach shall not be used, conse­quently it was not pursued. Instead, NASA has stated that the LO secondharmonics would be tolerated as long as they do not fall within +50 MHZ ofthe receive frequency when using specified ATS-F up-link and down-linkfrequencies. Accordingly, a computer tabulation was made showing allpossible combinations of such frequencies with separation of LO secondharmonics from the desired receive frequency (Table 10). The two asterisksat the extreme right show the only two combinations which could give anyproblem. As previously stated, even for this condition a slight adjustmentof the selected receive frequency would eliminate any possible problem.

Undesirable combinations are also shown graphically (Figure 47).

3.2.6.2 Performance Monitor (PM)

The Performance Monitor (PM) is a double-conversion up-converter whichconverts a 70-MHz signal to any selected region of the 3.7 to 4.2 GHzreceive region. A block diagram is shown in Figure 48.

79

6.46.0 6.1 6.2 6.3

TRANSISTOR FREQUENCY (GHZ)

-FORBIDDENFREQUENCYTRANSLA-

------------___ - nONS

//1

II

/' I

/ II- IIII3.9

5.9

4.3

,....N

::I: 4.2(!).........

>-uz:lJ.J:=>0- 4.1lJ.Jex:l.J..

ex:lJ.J>-......lJ.J

4.0ulJ.Jex:

Figure 47. Translator Transmit-Receive Frequency combinations That ProvideUndesired Spurious Responses Due to Local Oscillator

80

+28V

RFI

+20V

-RE

GULA

TOR

FILT

ER

70MH

z+2

0MH

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PAD

3dB

3.7:

-4.2

GHz

-30

dBm

TOOU

TPUT

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-_..

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-27

dBm

MXR

BAND

PASS

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0dB

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3dB

-15

dBm

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-8dB

mo

dBm

+1dB

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.32

GHz

+10

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SS2.

0dB

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90MH

z+6

dBm

+3dB

>8

0dB

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80etB

0.97

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GHz

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48

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Significant electrical characteristics are:

Signal input:

FrequencyLevelInput impedanceVSWR

Signal output:

Frequency

LevelImpedanceVSWR

Passband characteristics:

FlatnessGroup Delay:

Combined linear andparabolic ripple

Amplitude linearity

Spurious

Local oscillator inputs:

LO # 1FrequencyLevel

LO # 2FrequencyLevel

82

70 +20 MHzo dBm +1 dB75 ohmsLess than 1. 5: 1

Any selectable frequency withinrange of 3.7 to 4.2 GHz.Frequency setability determinedby resolution of synthesizer

10 Hz x 72 - 720 Hz-30 dBm +1 dB50 ohms

.1. 2 : 1 maximum

+0.2 dB over any 40 MHz

1 nanosecond over 40 MHz0.5 nanoseconds peak-to-peakFor two tones at input of 0 dBm3rd order intermod's at outputwill be at least 17 dB belowdesired output.All spurious signals within+100 MHz of desired outputfrequency will be at least60 dB below desired outputsignal.

90 MHz+6 dBm +3 dB

39 to 46.2 MHz+6 dBm +3 dB

Both LO signals will have phasenoise characteristics such thatoutput single sideband phase noisein a I-HZ bandwidth, 1 MHz fromcarrier, will be at least 100 dBbelow desired signal.

3.2.7 Miscellaneous Receiver Test Aids

A number of miscellaneous test aids, loops, sources, etc. may benecessary in trouble shooting or as part of planned experiments. Ageneral block diagram, extracted from the Rosman overall system blockdiagram, is shown in Figure 49. Signal paths for these various sourcesare self explanatory but details of the sources are discussed in thefollowing paragraphs.

3.2.7.1 Noise Sources (614-01535)

A solid state noise source is provided to facilitate noise tempera­ture measurements by an operator in the instrumentation room (Figure 49).The noise source (Figure 50) is an AIL Type 76 (Part Number 07616),which operates on a +28 VDC command. Once the noise source has been in­stalled with all interconnecting cable (RG 214), its power output may becalibrated at theparamp input switch with a variable attenuator (ARRA4674-50L) and flap attenuator. The flap attenuator is part of the cooledpreamp assembly and acts as an accurate room-temperature noise source.Once the calibration is complete, the operator can remotely select thenoise source for the Y-factor measurement. Noise source characteristicsare:

Frequency range:Excess noise ratio (ENR):Load decoupling:Power required (fired):Output connector:Input connector (power):Size (including connectors):

1.0 to 12.5 GHz15.5 +0.5 dB20 dB+28 VDC/30 rnaType "N"BNC1 x 1 x 6 inches

3.2.7.2 Tracking Signal Source Splitters (Rosman Only)

At Rosman (only), there presently are two Merrimac magic tees thataccept a tracking test signal and split it into ~X, ~Y, and L channelsignals (Figure 49). This signal can then be applied to the respectivetracking channels through Martin Marietta-supplied directional couplers(MM supplies new tracking channel couplers for all three sites).

The Merrimac magic tees are located near the monopu1se (tracking)down-converter near the base of the feedcone. This test equipment will beleft as is when new tracking do~converters are installed.

83

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3.2.7.3 Detector/DC Amplifiers for Cooled Amplifier ~ojave Only)

At Mojave (only), a coaxial diode detector mount, followed by aPhilbrick DC amplifier, is mounted on a support member of the feedcone(Figure 49). This test equipment is used to remotely monitor gain-bandwidth of the cooled preamplifier when a swept signal is applied to thepreamplifier input. This capability will be retained as-is, when MartinMarietta modifies the feedcone for extended frequency range (3.7 to 4.2GHz) operation. The swept display can be accomplished when the functionswitch on the control panel (4Al) is in one of the following "low noiseamplifier input" positions: (1) frequency translator, (2) performancemonitor, or (3) noise source, and the output switch of the low noiseamplifier is in the override position. This switching arrangement allowsthe cw test input, to which the frequency sweeper is applied, to beconnected through a 20 dB coupler to the cooled preamp input, whilethe post-amp output is connected to the diode detector mount.

3.2.7.4 CW Test Input Switch (Rosman Only)

Martin Marietta is providing a switch in the CW test input line thatpermits a test signal, or the Hughes RFI multiplier, to be switched inthrough the 20 dB coupler to the input of the cooled preamplifier. Con­trol for this transfer switch is located on the monitor and controlpanel (4Al) and is labeled "test input multiplier in-out." This featureis being provided at Rosman only.

3.2.7.5 Attenuator Calibrator

Martin Marietta is providing one AIL Type 137 RF attenuator cali­brator (Figure 51). This item is presently employed in the antennalab to make accurate, low insertion loss, feed line component measure­ments (OMT, diplexer, transmit reject filters, bandpass filters). Inaddition to insertion loss measurements, fhe Type 137 receiver can beused for the Y factor measurement (noise temperature) at 70 MHz, theoutput frequency of the communications down-converter. Mechanics of theY-factor measurement were described in Paragraph 3.2.2 of this report;other features may be found further in this section.

No plans have been made for installing this equipment at any of thesites. Present plans are to ship this item to NASA-GSFC.

3.2.8 Local Oscillator System

Figure 52 shows local oscillator generation at all sites. Generally,communication channel local oscillator frequencies are referenced back tothe 5 MHz station standard, and tracking local oscillator signals aregenerated from independent sources. Therefore, all communication localoscillator signals will exhibit the same long term frequency stability asthe 5 MHz station standard, e.g., 5 parts in lOla for 24 hours and 1 partin 108 per year. Tracking channel local oscillator signals will have nomore than +5 parts in 109 per day. The VCXO and multiplier combinations

86

T

T

TTTTrrrrrrrrr

.­-roUco.-+Jro::JC(J)

~<:(

l.J..e:::

Simple Operation - Only 4Controls. Single-step Range - 0.01 to 100 dB • Broad-band Frequency - Coverage 10 MHz to 40 GHz

Having Calibration Problems?Here's a foolproof, simple Attenuation Calibratorthat anyone can use

IF substitution systems are classified aseither series or parallel dependin~ onwhether the attenuation standard IS inseries with the main signal path or in aparallel reference path.

The series method provides the user withsuch simplicity of operation as to makethis approach hi~hly desirable; however,varying system noise levels have restrictedthe useful measurement range of seriessystems compared with that usable withparallel systems.

AIL has now developed a completely newIF series-substitution system that over­comes past restrictions and greatly. in­creases the sin~le-step measurementrange, while retaining the inherent sim­plicity for the user. This new improvedseries-substitution system, which includesseveral new exclusive user features, offersthe following advantages:

WIDE RF RANGELi!'l1ited only by availability of suitablemixers.

RF Range

Specifications

10 MHz to 40 GHz(determined by mixer used)

Attenuation Measurement RangeSingle-step measurement 100 dB (maximum)

Range versus Accuracy

HIGH ACCURACYFrom 0.007 dB for small attenuationmeasurements to a maximum of 0.4 dBfor a 100-dB range. For increased ac­.curacy the reference attenuator is easilyremovable for calibration at NBS.

EXCEPTIONAL RESOLUTIONExpanded scale operation provides sensi­tiVity of 0.008 dB per division.

SIMPLE OPERATIONFewer controls and adjustments greatlyreduce personnel training and technicalqualifications.

INTERNAL MODULATIONRequirement to modulate external signalsource is eliminated, thereby reducingequipment complexity and personnelhazard.

INTERNAL AFCCompletely integrated AFC eliminates re­quirement to control the frequency ofexternal signal sources.

EXCLUSIVE uPROHIBITFUNCTION"Prevent.s the operator from making falsemeasurements if system falls out of AFC.

.ALL SOLID STATEProvides highest stability and lowestmaintenance costs. .

Attenuation Step (dB)1020408090

100Attenuator

RangeAccuracy

ResolutionMeter Functions

Meter ResolutionsNormalExpand

Automatic Frequency ControlFrequency error reductionRF signal frequency driftMinimum input signalMaximum input signal

Dimensions (inches)Power RequiredPrice

Overall Accuracy (dB)±0.04±0;05±0.07±0.20±0.30±0.40

o to 100 dB±0.005 dB/10-dB increment + 0.03 dBattenuator accuracy inCluded In overall accuracy

0.01 dB/divisionCrystal currentDetectordevelReference level

0.2 dB/division0.008 dB/division

1000 to 1 (min.)10 Mt-!z-115 dBm into mixer-15 dBm into mixer·19-13/16 wide by 9-7/8 high by 3.3 deep115/230 VAC ± 10%, 50 to 400 Hz, 40 watts$3,500 F.O.B. Deer Pa.rk, New York

Figure 51 (contipued)

~88

-

--

-

INTERNAL AUTOMATICFREQUENCY CONTROLThe Type 137 consists of a dual-conver­sion system where AFC is maintained inthe second local oscillator. This providesthe user with a completely integratedsystem and eliminates loop gain adjust­ments, response time adjustments, andfrequency control of external oscillators.

A front-panel indicator provides the userwith a positive indication of proper AFCoperation.

SOLlD·STATE CONSTRUCTIONThe Type 137 is the only completely tran­sistorized instrument of its type. It pro­vides a degree of stability, reliability, andlow mainterance previously not available.

Exclusive Features

PLUG·IN MIXERS FOR BROADRF COVERAGEThe external preamplifier is designed toaccept an entire series of mixers by asimple mechanical plug-in arrangement.AI.L makes ayailable a series of Type 135mixers covering the frequency range from10 MHz to 40 GHz. The user need onlyprovide a signal source and localoscillator.

METER TIME CONSTANTThrough a unique circuit design, the de·tector time constant is automatically in·creased as the signal·to·noise ratiodecreases. This ensures that the useralways has the optimum time constantfor his measurement and eliminates theneed for a manual control.

PROHIBIT FUNCTIONIn addition to the front·panel AFC indi·cator, the Type 137 includes an exclusivefunction that causes the meter indication'to go to zero jf the unit drops out ofAFC. This feature makes the instrumentfail·safe since it is virtually impossibleto m~~e a measurement under improperconditions.

NOISE STABILIZATIONA unique internal noise·stabilization cir·cuit eliminates apparent nonlinearities inthe detector thereby increasing measure·ment range and permitting recovery ofsigna Is well below noise.

A convenient null system is provided toenable the operator to set the level of/thebackground noise.

-

LSIMPLIFIED SYSTEM BLOCK DIAGRAM

Figure 51 (continued)

89

TABLE OF TYPE 135 MIXERS

AVAILABLE FOR DIRECT PLUG·IN OPERATION WITH THE TYPE 137

FrequencyPIN Range (GHz) Price

TYPE 135 COAXIAL MIXERS13508 0.01 to 1.0 $495.0013504 1.0 to 2.0 290.0013505 2.0 to 4.0 290.0013506 4.0 to 8.0 290.0013507 7.0 to 11.0 495.0013509 3.6 to 4.2 290.00

TYPE 135 WAVEGUIDE MIXERS13522 3.7 to 4.2 750.0013523 4.4 to 5.0 750.0013524 5.4 to 5.9 605.0013525 5.9 to 6.5 605.0013526 6.5 to 7.5 605.0013527 7.5 to 8.5 525.0013528 8.5 to 9.6 450.0013529 8.8 to 10.25 525.0013531 10.0 to 12.4 800.0013532 12.4 to 14.0 580.0013533 13.5 to 15.6 580.0013534 15.0 to 17.0 580.0013538 23.0 to 25.0 825.0013539 34.0 to 36.0 950.0013541 17.0 to 19.7 650.0013542 25.0 to 29.0 1,200,0013543 29.0 to 34,0 1,200.0013544 36.0 to 40.0 1,250.0013545 19.7 to 23.0 950.0013546 8.2 to 12.4 750.0013547 12.4 to 18.0 675.00

.-

111ll,

lI

lllI

-Prices and specifications subject to change without notice.

4-WAYPOWER

...~---.. 2.82-3.32 GHz

TRACKING CHANNEL1ST LO

X72MULTIPLIER

PART OF

TRACKING FREQUENCYSYNTHESIZER

614 01500 OR

..,I

) - 614-01526 DIVIDER614-01540

STABLE XTAL744 MHzOSC. AND 744 MHz 4-WAY

MULTIPLIER POWER TRACKINGPART OF DIVIDER CHANNEL 2ND LO

614-01526

PERFORMANCE

90 MHz MONITOR X9 810 MHz PERFORMANCEMULTIPLIER

I PART OF MON ITOR 1ST LO

X18 614-01543MULTIPLIER

PERFORMANCE

t MONITOR 2.82-3.32 GHz

P.M. AND F.r. r X72 MULTII PART OF PERFORMANCE

614-01543 MONITOR 2ND LO

5-MHz 5 MHz POWER... DIVIDER FRE,. SYNTH.~VCXO 614-015403

NOTE 1 FREQUENCY 1.7-2.7 GHz

t ITRANSLATOR FREQUENCY

MULTIPLI ERSPART OF TRANSLATOR LO

614-01543

'I.

5-MHz COMM. CH. 1 COMM. CH. 2

STATION FREQ. SYNTH X72 MULTI COMM. CH.

I PART OFSTANDARD 614-01540 614-01525 2.82-3.32 GHz 1ST LO, I I

POWER I COMM. CH. 2 COMM. CH. 25-MHz FREQ. SYNTH X72 MULTI COMM. CH. 2

~VCXO

DIVIDER PART OF4 I 614-01540 614-01525

2.82-3.32 GHz 1ST LO

t I810 MHz COMM.

CDMM. CH.CH. 1 2ND LO

X18 90 MHz POWERMULTIPLIER X9 MULT. DIVIDERI 614-01 518A

810 MHz COMM.

G;EQ;;Y;;;;RA;;- r-----'"""I614-01560 5-MHz

STABLEXTAL OSC.

L ---lNOTE 1: THIS SYNTHESIZER WILL BE

SHARED WITH COMM. CH. 2

CH. 2 2ND LD

Figure 52. Local Oscillator Generation System - All sites

91

employed will meet the following required short term stability and phasenoise requirements:

Tracking channels:

1 8 parts in lOll for 1 second averaging

2 Phase noise will be at least 50 dB below 1 radian from 20 Hzto 1 kHz when measured with a 3-Hz analyzer bandwidth.

3 Phase fluctuation noise will be at least 70 dB below1 radian from 1 kHz to 1 MHz.

Communications channels (including performance monitor and frequencytranslator) :

1 The signal-to-phase noise in any 1 Hz bandwidth at a separa­tion from-the carrier of 10-1000 Hz (excluding powerlinefrequencies) will be at least 48 dB and, at a separationof 1000 HZ, the ratio will be at least 80 dB (Figure 53).

2 The signal-to-phase noise ratio measured in any 3 kHz band­width between 1 kHz and 1 MHz away from carrier will be atleast 55 dB (Figure 53).

3 When using the Fluke 6l60A synthesizer, the signal-to-phasenoise ratio in any 1 Hz bandwidth at a separation of 1 MHzor more from the carrier is expected to be at least 100 dB(Figure 53) .

3.2.8.1 Synthesizers

A major advantage of the new receiver system is the ability to setreceive frequencies in the operations room by the simple manipulation offront panel rotary switches, each of which selects a decimal digit of thebasic local oscillator source. - Multiplication of this basic source pro­vides the ultimate local oscillator frequency.

To accomplish this, two different frequency synthesizers are beingprovided under the contract as follows:

1 Two Fluke Model 645A/CF synthesizers (Figure 54) with10 Hz resolution (Martin Marietta Specification 614-01500)

2 Four Fluke Model 6l60A synthesizers (Figure 55) with 1 Hzresolution (Martin Marietta Specification 614-01540).

This represents a change in both quantity and types of synthesizersfrom the original contract which was based on supplying nine Fluke 645A

92

40

50

60

N:c........

70co-0~

0......~ 800:::

z:........(/)

90

100

110

120

SPECIFICATION LIMIT/'

~~

'"'"~ FLUKE MODEL 6160A

+MULTIPLIER

'"~CHARACTERISTIC

FLUKE MODEL 645~r\. '\+MULTIPLIER

CHARACTERISTIC \.,\

\

101

102 103 104 105

OFFSET FROM CARRIER-HZ

Figure 53. Worst Case Receiver Local Oscillator to Single

Sideband Phase Noise

93

units (three per site). The change was brought about by Contract Amend­ment Number 1 which provided for a maximum of six synthesizers. Purposesfor the change included:

1 Reduce the total number of synthesizers being furnished byseveral contractors because of plans to time-share units, and

2 Provide at each site at least one communications channelsynthesizer that would have superior phase noise characteristicsat 1 MHz or more away from center frequency.

From Figure 56 which shows the phase noise characteristics ofboth units versus frequency, it can be seen that the 645A provides slightlybetter performance out to approximately 200 kHz from the carrier, but thenreaches a floor beyond which no further improvement occurs. The 6l60A,on the other hand, provides significantly better performance at 1 MHz ormore away from the carrier.

Since the multiplication factor for the communications down-converterlocal oscillator is 72, the multiplication process can be expected todegrade the single sideband phase noise by at least:

degradation (dB) = 20 log 72 = 37 dB.

This would result from a perfect multiplier. To account for additionalnoise, which may be contributed by the multiplier itself, another 3 dBof degradation is assigned to the multiplier itself with the result thatthe actual local oscillator signal is expected to have a single sidebandphase noise approximately 40 dB poorer than represented by the curves ofFigure 56.

The multiplication factor of 72 also implies that receive frequenciescan be set to a resolution of 720 Hz for the 645 model, or 72 HZ for the6l60A,both of which greatly exceed the requirement for 10 kHz resolution.

Both units have essentially identical performance in other respectsand are completely interchangeable, physically and electrically. Eithersynthesizer may be used in any application in the receiver system; how­ever, only the Fluke 6l60A synthesizer outputs will be routed through thepatch panels. Essential characteristics of both units are:

output frequency range

Resolution

output level

645

o to 50 MHz

10 Hz

+13 dBm maximum

95

6l60A

1 to 10 MHz10 to 159.999999 MHz

1 Hz in upper range

+13 dam maximum

1~ 103 1~ 1~FREQUENCY OFFSET FROM CARRIER

I

'"!

.~'"~

~\'\"I

\\ "645A, 6160A

\ \"a "'- ..

~-~r--- ___

----a

a

CURVES ARE FOR 1 Hz BANDWIDTH

a16

15

14

100

90

110

...J

~~'120~'c:z::::I.... -

:::E:oa:....:z:3-813CQ-c

Figure 56. Single Sideband Phase Noise Char~cteristics of Fluke

645A and 6l60A Synthesizers

96

output impedance

Spurious outputs

645

50 ohms

6l60A

50 ohms

Nonharmonic

Harmonic

Signal-to-phase noise ratio

100 dB below 60 dB belowfundamental fundamental

30 dB below 25 dB belowfundamental fundamental

(see Figure 56) (see Figure 56)

Both units have provision for locking their basic 5 MHz standardinput to the station standard, thus providing the long term accuracyidentical to the station standard.

Since the Fluke 6l60A was a model not yet in production, it wasnecessary to make its final selection contingent upon RFI tests to beperformed on the Fluke demonstration model by Martin Marietta. Thesetests made at Orlando, Florida on August 2, 1971, were in accordance withMIL-STD 461A and 462. The following tests were made:

RS03 Radiated Susceptibility 14 kHz - 1 GHzCSOl Conducted Susceptibility 30 Hz - 50 kHzCS02 Conducted Susceptibility 50 kHz - 400 MHzCS06 Conducted Susceptibility SpikeCEOl Conducted Emissions 20 Hz - 20 kHzCE03 Conducted Emissions 20 kHz - 50 MHzRE02 Radiated Emissions 14 kHz - 1 GHz

Of these tests, the following exceeded MIL Spec limits:

Test Spec Limit Test Measurement Excess-CEOl Broadband 90 dB/~v/20 kHz 125 dB/~v/20 kHz 35 dBCE03 Broadband (725 kHz) 78 dB/~amp/MHz 90 dB/~amp/MHz 12 dBRE02 Broadband (150 MHz) 56 dB/~v/l MHz 66 dB/~v/l MHz 10 dB

Although it was the opinion of Martin Marietta engineering that such"out of spec" conditions would have no adverse effect on any of the systemsnow installed or expected to be installed, NASA directed that the deficien­cies revealed in the RE02 and CE03 tests be corrected and that the CEOlproblem be corrected or improved.

Fluke Company subsequently quoted the correction for the RE02 andCE03 problem and have been directed to implement such corrections. Flukecompany gave the opinion that little could be done about the CEOl problem,but offered to perform a 4-week investigation, if funded, and then preparea fixed-price quote.

97

In lieu of the latter, Martin Marietta has elected to provide linefilters (Filtron Part Number FSR-304D) which probably will not completelycure the problem but will provide low frequency attenuation as follows:

2 kHz10 kHz14 kHz20 kHz

3 dB40 dB50 dB60 dB

Thus, for all but the lowest frequencies around 2 kHz and below, thefilter will provide adequate suppression. It is believed that no troublewill be encountered from any residual conducted interference at 2 kHz andbelow.

The filter is approximately 8 1/4 by 4 1/2 by 2 1/2 inches and willmount in the rack immediately behind the synthesizer.

3.2.8.2 Frequency Generator

With the normal exception of the tracking Channel local oscillatorgenerators, the local oscillator frequencies are phase-locked to the 5 MHzstation standard. These frequencies are generated by direct multiplicationof the 5 MHz sources, or the output of the sources are used to drivefrequency synthesizers, with the output from the synthesizers being multi­plied to the correct local oscillator frequencies. Due to NASA requirements,the tracking channel local oscillator generators are not normally phase­locked to the 5 MHz station standard, although a switch will be provided topermit selection of the station standard if desired.

figure 57 presents a block diagram of the local oscillator basicgenerator system. The frequency generator subsystem contains two VCXO'swhich are phase-locked to the 5 MHz station standard. One of the two 5 MHzVCXO's is provided to furnish the 5 MHz input for each of the communicationschannel frequency synthesizers. The output of the communications channelVCXO is also fed to the "x 18" mUltiplier which furnishes 90 MHz to thecommunications channel second oscillator generator. To prevent the possi­bility of phase noise cancellations when the performance monitor is beingused, a separate 5 MHz VCXO, phase-locked to the frequency standard, pro­vides a 5 MHz source to the "x 18" multiplier that furnishes 90 MHz to theperformance monitor second local oscillator generator. Any phase noisegenerated in the receiving local oscillator system and performance monitorlocal oscillator system is uncorrelated, since the same source is not usedto generate the local oscillator signal for both performance monitor andcommunications down-converter. The modules employed in the frequencygenerator were previously designed under the NASA L- and S-band transmittercontract.

The Performance Monitor second local oscillator generator and FrequencyTranslator local oscillator generator operate from the same frequencysynthesizer. A common synthesizer may be employed, since the performance

98

PERF

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511

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5-M

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VCXO

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MHz

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monitor and frequency translator are not used simultaneously. Furthermore,it is the understanding of Martin Marietta that it is NASAls intent to sharethe synthesizer of the Performance Monitor/Frequency Translator with thesynthesizer requirement for Communications Channel No.2.

The front panel view of the frequency generator is shown in Figure 58.

3.2.8.3 Local Oscillator MUltipliers

The relationship of the local oscillator multipliers to the fre­quency synthesizers and frequency generators is depicted in Figure 52.It was originally intended that these mUltiplier assemblies would beseparate entities; however, it has since been decided to include suchmultipliers inside respective down-converters as well as the PerformanceMonitor/Frequency Translator. The only exception is that the "x 9"multiplier used, to generate the 810 MHz second LO for the communicationsdown-converters (614-01518-A), will be a separate assembly. However, sinceall down-converters, the Performance Monitor/Frequency Translator, and the"x 9" multiplier have been subcontracted to Aertech, description of themultiplier packages is discussed elsewhere with the major assembly they area part of or with which they are used.

100

86

1-A

FREQUENCY GENERATORRECEIVERS

,----- PHASE LOCK INDICATORS----......

f SYNTHESIZER REFERENCES -,

PEfilFOR"'''NCECONMUNICATIONS MONITOR

r<4~ ""HZ CRYSTAL OSCillATOR IPERFORMANCE

COMMUNICATIONS MONITOR

rB

o o o ol

sT.....nON

TRACKING

STANOAF:lD

INTERNA,L

PERfOR .....NCE:MONITOR

90 MHZ TEST

-I ASSY

CDMNUNI(ATlON5

\

POWER

o

Figure 58. Front Panel of Frequency Generator

101

3.2.9 Interconnection and Cabling

3.2.9.1 Intersite RF Cables

Where possible, existing cables will be employed for RF cablingat the various sites. Additional cables required will be supplied. Allavailable drawings and reports were reviewed to identify existing availablecables, and a cable plan for each site is presented in this section. Allrequired interconnecting RF cables are shown, existing cables are identifiedand ~ssigned, and any new cables required are itemized. In addition, thecable lengths and attenuations are presented for each signal path.

Figure 59 shows all intersite RF cables for the Rosman station, withtheir cable numbers and characteristics. Table 11 presents the cablelengths and cable attenuations for each signal path.

Figure 60 shows intersite RF cables for the Mojave station and Table12 presents cable lengths and attenuations.

Figure, 61 shows intersite RF cables for the TGS station and Table 13presents cable lengths and attenuations.

These figures and tables' represent an updating of the RF cable plancontained in Section 4.6 of the Design Review Report, OR 11,239, datedAugust 1971.

3.2.9.2 Control/Monitor Cables (Inter- and Intra-Site)

Various multiconductor shielded cables will be used to provide thevarious control, monitor, and power circuits required by ,the receivingsystem. These cables interconnect the control and monitor unit in theins~rumentation room with the junction box in the antenna and the variousremote switches and units located at the antenna site. Figure 62 showsthe control and monitor cables that will be installed at each of the sites.There will be two 50-conductor cable assemblies (W10 and Wll) connectingthe control and monitor unit with the junction box. Cable W10 will provideall monitor circuits and Wll will contain the control circuits. In addition,Cable 23 between the junction box and the Performance Monitor/FrequencyTranslator unit is a 50-conductor cable assembly. These cable assemblieswill use ITT (P/N 8864) 50-conductor, 20 AWG cable which has an overallbonded shield and outer neoprene jacket.

All other junction box interconnecting cable assemblies shown inFigure 62 will use ITT (P/N 8863), la-conductor, 20 AWG cable. This cablealso has an overall bonded shield and outer neoprene jacket.

3.2.9.3 Junction Box

The junction box serves as an interconnecting and distribution centerfor all control/monitor circuits and +28 VDC power control and distribution toall units (except paramp) located at the antenna site. It is located in

102

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TABLE 11

Rosman RF Intersite Cable Attenuation

Path 1: Signal Freq: 136 MHz

1. Total Path Length

(a) 7/8" styro, (50 n )(b) RG9B

2. Total Attenuation

(a) 7/8" styro, (50 n )(b) RG9B

2000 feet200 feet

10 dB5 dB

2200 feet

15 dB

Path 2: Signal Freq: 136 MHz

1. Total Path Length

(a) 7/8" styro (50 n)(b) RG9B

2. Total Attenuation

(a) 7/8" styro, (50 n )(b) RG9B

2200 feet

2000 feet200 feet

15 dB

10 dB5 dB

Path 3: signal Freq: 136 MHz

1. Total Path Length

(a) 7/8" Styro (50!l)(b) RG9B

2. Total Attenuation

(a) 7/8" styro (50!l)(b) RG9B

400 feet20 feet

2.4 dB0.5 dB

500 feet

2.9 dB

Path 4a: Signal Freq: 136 MHz

1. Total Path Length

(a) 7/8" Styro (50 n(b) RG9B

2. Total Attenuation

(a) 7/8" Styro (50 n )(b) RG9B

104

500 feet

480 feet20 feet

2.9 dB

2.4 dB0.5 dB

TABLE 11 (Continued)

Path 4b: Signal Freq: 136 MHz

1. Total Path Length

(a) 7/8" Styro, (50 m(b) RG9B

2000 feet200 feet

2200 feet

2. Total Attenuation 15 dB

(a) 7/8" Styro, (50 rl) 10 dB(b) RG9B 5 dB

Path 5: Signal Freq: 70 MHZ

l. Total Path Length 500 feet

(a) 1/2" Foam , (75 rl) 480 feet(b) RG13 20 feet

2. Total Attenuation 4.0 dB

(a) 1/2" Foam, (75 m 3.6 dB(b) RG13 0.4 dB

Path 6: Same as 5

Path 7: Signal Freq: 50 MHz

l. Total Path Length 500 feet

(a) 1/2" Foam (75 m 480 feet(b) RG13 20 feet

2. Total Attenuation 3.2 dB

(a) 1/2" Foam (75 m 2.9 dB(b) RG13 0.3 dB

Path 7a: Same as 5

Path 8: Signal Freq: 90 MHz

l. Total Path Length 500 feet

(a) 1/2" Foam (75 rl) 480 feet(b) RG13 20 feet

2. Total Attenuation 4.3 dB

(a) 1/2" Foam (75 rl) 3.9 dB(b) RG13 0.4 dB

105

TABLE 11 (Continued)

Path 9: Signal Freq: 90 MHz

l. Total Path Length 400 feet

(a) 1/2" Foam <-75 m 300 feet(b) RG2l6 100 feet

2. Total Attenuation 3.2 dB

(a) 1/2" Foam (75 n) 1.8 dB(b) RG2l6 (75 m 1.4 dB

Path 10: Same as 7

Path 11: Signal Freq: 500 MHz

l. Total Path Length 400 feet

2. Total Attenuation 5.6 dB

Path 12: Same as 7

Path 13: Signal Freq: 3.7 to 4.2 GHz

l. Total Path Length 390 feet

(a) Elliptical Waveguide 310 feet(b) 1/2" Superflex Coax 80 feet

2. Total Attenuation

(a) Elliptical Waveguide 2.4 dB(b) 1/ 2" Super Flex Coax 9.6 dB(c) Misc. Connectors 1.0 dB

106

70-MHzINPUT

0W1325 FREQUENCY

CD GENERATOR

MW32

MW33

(1/2" FOAM, 75.o./RG216)

2 COMM. CHANNEL 1ST L.O.)

(1/2" FOAMFLEX, 75.o./RG215)

CHANNEL 2ND L.O.'S)

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90 MHz (PERF. MONITOR L.O.)

W1319 (1/2: FOAM FLEX, 75.o./RG216)

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70 MHz IN

X9 MULT.

X72 MULT.

X72 MULT.

20-50 MHz (NO.X72 MULT.

_~NEW~

liOII...._--------250 o----------I.

ANTENNA

TO MIXERS

r-- - --:: - ~ 6X, 136 MHzCDI---l

DOWNCONVERTER\ W1310 (RG9 (50.0.) W1329\

6Y 6Y, 136 MHz CDDOWN CONVERTER W1309 (RG9 (50.0.) W1328

TO TRACKING

0 CHANNEL RECEIVERSMOL 6POL, 136 MHz

DOWNCONVERTER W1311 (RG9 (50.0.) W1330

01~CHANN.~ CHANNEL, 136 MHz

DOWNCONVERTER W1308 (RG9 (50.0.) W13271

NO. 1 COMM. CHANN. NO.1 COMM. CHANNEL, 70 MHz CDDOWNCONVERTER W1322 W1326

TRANSMITTER

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G)L.O.)20-50 MHz (PERF. MON. AND FREQ. TRANSL.

W1701 (RG214 (50.0.)

NOTE:CIRCLED NUMBERS ARE SIGNAL PATH NUMBERS.

Figure 60. Intersite RF Cables - Mojave

107

TABLE 12

Mojave RF Cable Attenuation

Path 1: Signal Freq: 136 MHz

1. Total Path Length 250 feet

(a) RG9 250 feet

2. Total Attenuation 6.3 dB

(a) RG9 6.3 dB

Path 2 : Same as 1

Path 3: Same as 1

Path 4: Same as 1

Path 5 : Signal Freq: 70 MHz

1. Total Path Length 250 feet

(a) 1/2" Foam Flex (75 n) 230 feet(b) RG2l6 (75 n) 20 feet

2. Total Attenuation 2.0 dB

(a) 1/2 Foam Flex (75 n) 1.6 dB(b) RG2l6 (75 n ) 0.4 dB

Path 6: Same as 5

Path 7: Signal Freq: 50 MHz

l. Total Path Length 250 feet

(a) RG2l4 (50 n) 250 feet

2. Total Attenuation 3.5 dB

(a) RG2l4 (50 n) 3.5 dB

Path 7a: Same as 5

Path 8: Signal Freq: 90 MHz

l. Total Path Length 250 feet

(a) 1/2" Foam Flex (75 n ) 230 feet(b) RG2l6 20 feet

2. Total Attenuation 2.3 dB

(a) 1/2" Foam Flex (75 n) 1.9 dB(b) RG2l6 0.4 dB

Path 9: Same as 8

Path 10: Signal Freq: 50 MHz

l. Total Path Length (RG2l4) 315 feet

2. Total Attenuation 4.4 dB

Path 11: Same as 10

Path 12: Same as 11

108

TO TRACKINGCHANNEL RECEIVER

FREQUENCYGENERATOR

70-MHz INPUT

FREQ. SYNTH.(GFE, TEST)

FREQ. SYNTH.(TRACKING)

FREQ. SYNTH.(COMM. NO.1)(RG214, SO n ) (TW 42A, B, C)

COMM.CHANNEL 1ST L.O.)

(RG223, RG214, Son)

QCHANNEL 1ST L. 0.) (TW 41A, B, C) '::..I

NEW - (RG214, Son)

D. POL, 136 MHz (TW 33A, B, ~) ~

NEW __ (RG214, Son) (TW 43A, B, C)

NEW_

90 MHz (COMM.

NEW _ (RG214, Son) (TW 38A, B, C)

NEW __ (RG214, Son)

NEW __ (1/2" FOAM, RG216) 17\90 MHz (PERF. MONITOR L.O. 'S) \!..)NEW -- (RG214, Son) t:'\20-S0 MHz (TRACKING 1ST L.O. 'S) (TW 40A, B, C) \!./

20-S0 MHz (NO.

20-S0 MHz (NO.2 COMM. CHANNEL 1ST L.a.)

NEW - (RG214, SOn) r;;\1: CHANN., 136 MHz (TW 34A, B, C) \:..J

0 '----,D. x, 136 MHz (TW 31A, B, C) I1-f---:-:N":::EWO:---:.=-----;(::-:RG:::2":"""14:-,-:S::":0-=n):---------I7'\--t-.-..

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X9 MULl.

X72 MULT.

X72 MULl.

X72 MULT.

NEW _ (RG214, Son)

NO.1 COMM. CHANN. 1-.J-_N_0_._1_CO_M_M_._C_HA_N_N_EL_,_70_MH_Z_(_T_W_3_S_A,_B_,_C_)__0_S_.J-..}DOWN CONVERTER NEW _

r;'\ TO COMM. CHANNEL

NO.2 COMM. CHANNEL, 70 MHz (TW 36A, B, C) \::.J RECEIVERS

NEW _ (1/2" FOAM, RG216/7Sn ) I20-S0 MHz (PERFORMANCE MON. ~ ~

AND FREQ. TRANSL. L.O.) (TW 37A, B, C) ~ ~

NOTE:CIRCLED NUMBERS ARE PATH NUMBERS.

TOMIXERS

~~--

,-

Figure 61. Intersite RF Cables - TGS

109

TABLE 13

TGS RF Cable Attenuation

Path 1: (2.3 dB/100 feet) (175 feet) = 4.0 dB

Path 2 : Same as 1

Patb 3: Same as 1

Path 4: Same as 1

Path 5: Signal Freq: 70 MHz

1. Total Path Length 195 feet

(a) 1/2" Foam 145 feet(b) RG216 50 feet

2. Total Attenuation 1. 93 dB

(a) 1/2" Foam 1.03 dB(b) RG216 0.9 dB

Path 6: Same as 5

Path 7: (1.4 dB/lOa feet) (195 feet) = 2.73 dB

Path 7a: Same as Path 5

Path 8: (2. a dB/lOa feet) (190 feet) = 3.8 dB)

Path 9: (1.4 dB/100 feet) (190 feet) = 2.66 dB

Path 10: Signal Freq: 90 MHz

1. Total Path Length 190 feet

(a) RG223 (50 m 35 feet(b) RG 214 (50 m 155 feet

2. Total Attenuation 4.57 dB

(a) RG223 1.47 dB(b) RG214 3.10 dB

Path 11: Same as 10

Path 12: Same as 10

110

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A number of precautionary measures have been taken to reduce thesusceptibility of control and monitor circuits to outside RFI. It is alsodesirable to reduce RFI from such sources as power supplies and switchand relay contacts. Another important requirement is the minimization ofRF coupling between units of the receive system due to common power supplyimpedances and stray .capacity and inductive coupling.

All of the control and monitor cables supplied by Martin Mariettahave an overall braided shield that is grounded through the shell of theconnectors to the unit cases. In addition, all connectors used on thejunction box and power supply box have integral EMI filters that exhibitthe attenuation versus frequency characteristics shown in Figure 67.These filter connectors, along with the RFI filtering built into thevarious units, provide adequate decoupling within the receiver system.

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117

3.2.10 Receiver Monitoring and Control

3.2.10.1 Control and Monitor (C&M) Unit

Control and monitor functions for the receiving system arecentralized in the receiver control and monitor unit. This is a rack­mounted unit, located in the Instrumentation Bldg. at Rosman and Mojave,and in the control center van at the TGS site. Primary purpose of theC&M unit is to control and monitor all remotely controlled switches andrelays in the receive system.

A rotary mode selection switch on the front panel (Figure 68)selects either the desired test mode or the normal "operate" condition.Each position of this switch activates a unique combination of switchingstates of the controlled relays. Each relay has verification contactswhich indicate its mechanical state. These verification signals areapplied to a logic gate which lights an indicator lamp (located at thecorresponding mode selection switch position) when the desired combinationof switch states is achieved. In addition to the test mode switch, there

-are a number of pushbutton switches with integral lamp indicators alongthe bottom of the front panel. These switches perform the various functionsindicated in Figure 68.

An individual override capability is provided for each remote switchcontrolled by the Test Mode Selector Switch. Realization of the capa­bility consists of seven 3-position toggle switches, each of which over­rides the Test Mode Selector Switch, selecting either of the two switchstates for any remote switch (Figure 69). These switches are locatedat the rear of the C&M Unit chassis. When all toggle switches are inthe center position, the rotary Test Mode Selector Switch takes over con­trol. A locking bar (Figure 70) can be switched down over the toggleswhen in this mid-position, thus assuring normal test mode control fromthe front panel.

To further explain the operation of the monitor and control panel,an examination of Figure 71 will show that, for various system con­figurations, the relays must operate in various combinations. Thisimplies a "logic" system which, for a given configuration "command"issues the appropriate subcommands to the individual relays. This isindeed accomplished by the Test Mode Selector Switch.

Thus, for the "operate" mode, the Test Mode Selector Switch issuesconunands to the "G" and "F" relays ordering them to be in the "true"state, as shown in Figure 71. The "H" relay receives a "true" stateconunand from the associated front panel pushbutton switch. Withordering of these three relays, the normal operating path is establishedas shown in the figure. The condition of all other relays is irrelevantand, for this operating mode, the condition of all other relays isnormally referred to as the "Don't Care" condition.

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To extend this further, a truth table was generated (Table 14)which shows the unique combination of switch states for each modeselected. With the Test Mode Selector Switch in each of the positionsshown, the corresponding relay states are set up, thus providing thedesired signal and signal path. The Form C verification contacts oneach switch feed back information to the C&M unit indicating themechanical state of that switch, and this information is converted toeither zero volts or +5 VDC corresponding with the switch state; e.g.,zero volts correspond with a, and +5 VDC with a). Logic N and gates areused to decode each unique combination of switch states. The decoderoutput drives an indicator lamp on the front panel located in proximityto the corresponding mode selector position.

Consider a typical control/monitor loop used for controlling andmonitoring Transfer Switch "G", located in the Paramp (Figure 72).Assume that the override switch (S14) is in its midposition, and theTest Mode Selector Switch is in the "operate" position. Since thetruth table calls for Stage "G", +28 VDe from the +28 V powersupply in the C&M Unit is applied to the appropriate coil of Relay K2in the junction box. This relay in turn applies +28 VDC to the desiredcoil of Transfer Relay "G." After mechanical switching occurs, theForm C contact (located in Relay "G") applies +28 VDC to Relay K2 inthe C&M Unit, which grounds (zero volts) the appropriate gate input.The +28 VDC energizing K2 in the C&M unit also lights the proper indi­cator lamp for Relay G, State "g" on the rear of the C&M Unit chassis.The override switch (S14) in the C&M unit can be used to position Relay"G" in either the "g" or "g" state, regardless what state the Test ModeSelector Switch calls for. In a like manner, other decks of the TestMode Selector Switch control other remote switches and verificationlogic is applied to the Nand gates. When the correct combination of supplyin switching states occurs, the panel lamp associated with the "operate"switch position lights, thus verifying that the desired signal pathhas been set up.

One deck of the Test Mode Selector Switch is used to activate adelay/one-shot multivibrator circuit which activates a relay thatinhibits all outgoing +28 VDC control signals while the Test ModeSelector Switch is being rotated. Approximately 1 second after switchrotation has stopped, normal operation is resumed. This preventsunnecessary activation of the remote relays during mode selection.

There are two power supplies in the C&M Unit: A Sorensen ModelQSAlO-2-2 supplies the +5 VDC for the logic circuits and a QSA28-6.0supplies +28 VDC to the remote switches and junction box relays.Both supplies meet MIL-I-26600, MIL-I-16910C, and MIL-I-6l8lD RFIspecifications.

123

TABLE 14

Test/Operate Mode Truth Table

Switch MonitoredA B CTest/Operate Mode D E F G

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3.2.10.2 "cw Test Signal" Multiplier Switching

Provision has been made for switching a multiplier "in" and"out" at the "cw Test Signal" directional coupler input. This feature,implemented at Rosman only, provides a pushbutton switch/indicator onthe C&M Unit panel, along with a coax transfer latching switch near themultiplier and CW Test directional coupler input. Figure 73 is a sche­matic of the multiplier switching. The 115 VAC power for the mUltiplieris supplied from the power supply box via a "multiplier in/out" controlrelay in the junction box. The Form C contacts on the Logus L07-2325transfer switch are used to provide a monitor of the switch states on thepanel of the C&M Unit.

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Rosman Site

Existing equipment racks 4Al and 6Al will be used for instal­lation of the equipment located in the Instrumentation Building. Figure74 shows the location of the equipment in the racks. The remote para­metric amplifier control, receiver control and monitor, two frequencysynthesizers (John Fluke Models 6160 and 645A), and the frequency gen­erator are located in the upper portion of Rack 4Al for ease of operatorcontrol and monitoring. The GFE patch panels will be located in Rack6Al in approximately the same position they now occupy. An additional5.5-inch-high panel (ATS FIG transmitter output control) will be locat­ed in the 28Al rack along with the junction box and the existing polar­ization switch control currently located in 24Al. The AIL ReceiverType 132, currently located in Rack 28Al, will be relocated to the 4Alrack.

The RFI transmission line (EWP 37 - Elliptical Waveguide) willenter the Instrumentation Building via the existing cable trough nearthe ceiling of the lower level. Unlike the other cables and lines thatgo up through the ceiling and into the false flooring, the RFI line willcontinue straight down the corridor along the ceiling. About one-thirdof the way down the corridor the line will gradually bend into the store­room through a small hole in the wire mesh barrier. The line will beterminated in a waveguide-to-coax transition just beneath the RFI rackslocated near the west wall of the building. The input to the RFI equip­ment will be connected to the RFI line via low-loss coaxial line drop­ped through a hole in the reinforced concrete floor. The hole will belocated and drilled by site personnel. The elliptical waveguide willbe held onto the ceiling with hangers spaced 3 feet apart.

Mojave Site

The equipment layout at the Mojave site, the same as at Rosman,is also shown in Figure 74. The receiver control and monitor assemblyat this site is the same as the unit located at Rosman except that theswitch for the test input multiplier has been deleted. The Mojave sitehas two John Fluke Model 6160 frequency synthesizers. The noise recei­ver (Ewan Knight Model EKLF-7000 Pr) will be moved from Rack 28Al toRack 4Al.

TGS Site

Existing equipment Racks V104A2 and V103A2 will be used forinstallation of the equipment in operations trailer. The remote para­metric amplifier control, receiver control and monitor, two frequencysynthesizers (John Fluke Models 6160 and 645A), and the frequency gen­erator are located in the upper portion of rack V104A2 for ease of oper­ator control and monitoring (Figure 75). The patch panels and the AILNoise Receiver will be located in Rack V103A2. The Teledyne Model 105Atracking receivers will be located in Rack VllOA2.

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5-1

ff

41

-1

Fig

ure

75

.L

oca

tio

no

fR

ak

-Mo

un

ted

Eq

uip

men

tO

pera

tio

ns

Tra

iler

-T

GS

12

9

3.2

.10

.4In

sta

llati

on

of

Co

ole

dA

mp

lifi

er

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og

enic

sS

yst

em

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man

Sit

e

The

hel

ium

com

pre

sso

r,co

mp

ress

or

by

pas

sm

an

ifo

ld,

ad

sorb

er

trap

,an

dad

sorb

er

by

pas

sm

an

ifo

ldw

ill

be

insta

lled

inth

ero

omat

the

base

of

the

an

ten

na

inth

esa

me

po

siti

on

as

the

ex

isti

ng

heli

um

com

pre

sso

r.E

xis

tin

gh

eliu

mli

nes

wil

lb

eu

sed

bet

wee

nth

eco

mp

ress

or

and

the

refr

igera

tor

un

itlo

cate

din

the

feed

con

e.T

helo

cal

am

pli

fier

co

ntr

ol

un

itan

dre

frig

era

tor

co

ntr

ol

un

itw

ill

be

insta

lled

inex

isti

ng

equ

ipm

ent

rack

slo

cate

din

the

equ

ipm

ent

room

beh

ind

the

an

ten

na

dis

h(F

igu

re7

6).

The

ante

nn

a-m

ou

nte

du

nit

co

nsi

sts

of

two

maj

or

sub

ass

em

bli

es:

(1)

The

refr

igera

tor/

vacu

um

dew

aras

sem

bly

,co

nta

inin

gth

eth

ree-s

tag

eco

ole

dp

ara

metr

icam

pli

fier

and

the

refe

ren

ced

co

ldlo

ad

,an

d(2

)th

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ctr

on

icas

sem

bly

co

nta

inin

gth

epu

mp

syst

em

,so

lid

-sta

teso

urc

e,

and

the

pum

pp

ow

erre

gu

lati

ng

loo

p.

Bo

thsu

bsy

stem

sw

ill

be

mo

un

ted

inth

efe

edco

ne

on

the

rota

tin

gta

ble

near

the

ex

isti

ng

co

ole

dp

aram

p.

The

un

ivers

al

po

wer

sup

ply

isals

olo

cate

do

nth

ero

tati

ng

tab

len

ear

the

ante

nn

a-m

ou

nte

du

nit

.T

here

mo

team

pli

fier

co

ntr

ol

un

itw

ill

be

locate

din

the

inst

rum

en

tati

on

room

inR

ack

4Al

(Fig

ure

74

).A

cces

sfo

rm

ain

ten

ance

and

testi

ng

has

bee

nco

nsi

dere

din

po

siti

on

ing

each

po

rtio

no

fth

esy

stem

.

Moj

ave

Sit

e

Insta

llati

on

at

the

Mo

jav

esit

eis

basic

all

yth

esa

me

as

at

Ros

man

ex

cep

tth

elo

cal

am

pli

fier

co

ntr

ol

un

itan

dth

ere

frig

era

tor

co

ntr

ol

un

itare

locate

din

the

feed

con

efo

rw

eath

er_

pro

tecti

on

clo

seto

the

ante

nn

a-m

ou

nte

du

nit

(Fig

ure

31

).

TGS

Sit

e

The

hel

ium

com

pre

sso

r,co

mp

ress

or

by

pas

sm

an

ifo

ldad

sorb

er

trap

,an

dad

sorb

er

by

pas

sm

an

ifo

ldw

ill

be

mo

un

ted

on

the

co

ncre

tep

adn

ear

the

base

of

the

an

ten

na

ped

est

al.

The

com

pre

sso

ris

desi

gn

ed

tom

eet

the

foll

ow

ing

en

vir

on

men

tal

co

nd

itio

ns:

Am

bie

nt

tem

pera

ture

op

era

tin

gra

ng

e

Hu

mid

ity

Rai

n

So

lar

rad

iati

on

Alt

itu

de

Snow

-25

to+

12

5°F

(-3

2°

to+

52°C

)

ato

10

0p

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en

t

Rat

eo

f4

inch

es

per

ho

ur

and

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mu

lati

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12in

ch

es

per

24h

ou

rs

350

BT

U/f

t2 /hr

ato

10

,00

0ft

6-i

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snow

load

.

13

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76

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Ros

man

New helium lines will be installed between the compressor andrefrigerator units mounted in the feed cone. The antenna-mounted unitwill be installed at the base of the feed cone (Figure 30). Thelocal amplifier control unit and refrigerator control unit will bemounted on the equipment racks located in the area behind the feedcone (Figure 77) •

3.3 Collimation Tower Equipment

3.3.1 Collimation Tower Electronics

Collimation tower electronics include a stable source assembly(Figure 78) and external attenuator panel assembly (Figure 79). Blockdiagram of the usual electronics configuration is shown in Figure 80.

The stable source assembly is in a pressurized container whichmay be mounted in the collimation tower equipment houses or installedin a standard relay rack in an aircraft for special dynamic trackingtests.

Five such assemblies will be furnished, one for each of thecollimation towers and two for the tracking aircraft. Only threeexternal attenuator panels will be furnished; these are intended foruse only in the collimation tower equipment houses.

The stable source assembly furnishes only one of 10 availablefrequencies at anyone time in the frequency range of 3.7 to 4.2 GHz.Frequencies available will be:

3.750000 GHz3.780000 GHz3.950000 GHz3.980000 GHz4.119599 GHz4.135956 GHz4.150000 GHz4.178591 GHz4.180000 GHz4.195172 GHz

Frequency stability of anyone oscillator will be better than1 part in 108 over any 3 millisecond period. Long and short termstability will be enhanced by operating the basic crystal oscillators(Greenray Model T3l6A in the 46 to 52 MHz range) continuously fromhighly regulated and low noise power supplies and from shock mountsthat isolate the oscillators from shock and vibration.

132

•1

Fig

ure

77

.In

sta

llati

on

of

Lo

cal

Am

pli

fier

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ntr

ol

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itan

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efr

igera

tio

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on

tro

lU

,it

-TG

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eed

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eR

oom

13

3

II

AM

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EA

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OM

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EE

NW

AY

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ME

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RD

FG

co.

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ER

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ure

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8.

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13

4

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ure

79

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45

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15

1.8

75

71

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152

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87

81

MH

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15

2.2

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39

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101

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80

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on

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13

6

The basic frequency of the oscillator in the 50 MHz region will beraised to the desired output frequency by applying it at approximatelyo dBm to the input of a "x80" multiplier. The multiplier providesfiltering sufficient to remove all spurious outputs to a level at least60 dB below the output signal.

The output of the multiplier (nominal 0 dBm) is raised to thedesired +20 dBm level by a Varian Model VTG 4420 TWT amplifier, whichis capable of operating over the frequency range of 3.7 to 6.4 GHz.The external attenuator panel may be used to adjust input and outputlevels to and from the TWT. The attenuators are both ARRA Model 4674-50Lunits having a range of 0 to 50 dB (calibrated in 1 dB increments) and anaccuracy of ~0.2 dB or 1 percent of dial reading, whichever is greater,at 3.950 GHz. Thus, the attenuators when manually operated can providean accurate change of level for calibrating receive equipment and formeasuring linearity.

The oscillator (and thus, the output frequency selection) relaysare RLC Model SR-5-R-D which have greater than 90 dB isolation at 50 MHz.Since the multiplier efficiency is a sensitive function of input level,the amount of leakage at the multiplier will be nil (less than -140 dBm) •Accounting for a TWT gain of 25 dB and isolation in the output relay ofat least 60 dB at 4 GHz, the undesired output from the stable sources,when the output relay is in the "simulator" position, will be in theorder of -175 dBm, a negligible amount.

Although five stable source assemblies will be furnished, only fourTWT's will be provided. Thus, one of the units must operate at theo dBm output level. Since two assemblies are provided for infrequenttracking-aircraft use, it is presumed that one of these units will not beequipped with TWT and may even serve as an emergency back-up unit for theother four.

Selection of "stable source" or "simulator," and selection of aparticular frequency from the stable source, will be accomplished byapplying a ground to the appropriate pin of J. This will normally beaccomplished via the remote control links at Mojave and Rosman. For TGSand for local manual control at any of the sites or in the aircraft, aswitch panel inside the assembly will permit local control. No damagecan result from simultaneous multiple operation of switches.

137

3.3.2 TGS Antennas and Controls

The collimation tower antennas and controls were supplied byScientific-Atlanta, Inc. in conformance with Martin Marietta Specification614-01534. The following items will be delivered to TGS:

1 Antenna (3.7 to 4.2 GHz) consisting of:

a Model 22-4 48-inch Parabolic Reflectorb Model 23-3.9/4 Antenna Feedc Model llA-3.9/M Coax-to-Waveguide Adapter

2 Antenna (5.9 to 6.4 GHz) consisting of:

a Model 22-3/M 32-inch Parabolic Reflectorb Model 23-5.9/3/M Antenna Feedc Model llA-5.8 coax-to-Waveguide Adapter

3 Model 5616-1-5136-R Polarization Positioner (Figure 81) (2)including:

a Coaxial rotary joint (DC to 12.4 GHz)b DC motor for variable speed and direction controlc Dual 1:1 and 36:1 synchro transmittersd All-weather operation

4 Model 4112 positioner Control unit (Figure 82) :

a Compatible with the Polarization Positionerb Capable of driving both positioners, one at a timec Front panel switch selection of either positionerd Single knob speed and direction controle Two 2-speed-position indicators, one for each positionerf Main line fuse and individual armature fuses located on

front panel

This equipment is nearly identical to that currently in use at Rosmanand Mojave. All components and interconnecting control cables have beenreceived and tested at Martin Marietta and are awaiting shipment to theTGS site.

Table 15 summarizes RF performance measured on each antenna. Allcharacteristics meet or exceed specifications.

138

...

...

...

...

Figure 81. Model 5616-1-5136-R Polarization positioner

Figure 82. Model 4112 positioner Control Unit

139

TABLE 15

Collimation Tower Antenna Performance

4 -GHz Antenna

Frequency VSWR Beamwidth (0 ) Sidelobe (db) Gain (dB) Axial Ratio (dB)

3.70 GHz 1.06 E - 4.8 E - 18.0 30.51

H - 4.0 H - 15.5

3.95 1.30 E - 4.3 E - 20.0 31.0 40

H - 4.5 H - 17.0

4.20 1.45 E - 4.0 E - 20.0 31.61

H - 4.1 H - 18.5

6 GHz Antenna

5.90 GHz 1. 22 E - 4.0 E - 21. 0 31.72

H - 4.3 H - 21. 0

6.15 1.46 E - 4.1 E - 22.0 32.0 37

H - 4.1 H - 19.0

6.40 1. 38 E - 3.6 E - 20.0 32.42

H - 4.0 H - 23.0

1

2

Calculation based on measurement at 3.95 GHz

Calculation based on measurement at 6.15 GHz

140

4.

SCH

EDU

LEO

FR

EMA

ININ

GA

CT

IVIT

IES

The

sch

ed

ule

for

tim

ely

com

ple

tio

no

fth

eco

ntr

act

isp

rese

nte

din

Fig

ure

83

.C

riti

cal

mil

est

on

es

inclu

de

sta

rto

fm

od

ific

ati

on

sat

Ros

man

on

10A

pri

lan

dat

TGS

on

22M

ay.

The

latt

er

date

isa

mo

nth

inad

van

ceo

fco

ntr

actu

al

date

san

dre

pre

sen

tsa

con

tin

gen

cyin

the

ev

en

tu

nfo

rese

en

tro

ub

les

dev

elo

pw

ith

the

TGS

syst

em.

The

maj

or

pro

cure

men

tth

at

co

uld

imp

act

the

fir

st

insta

llati

on

date

isd

eli

very

of

do

wn

-co

nv

erte

rsfr

om

Aert

ech

.T

his

deli

very

date

has

slip

ped

fro

m3

Dec

embe

r19

71to

app

rox

imat

ely

15Ja

nu

ary

19

72

.A

con

cen

­tr

ate

deff

ort

has

bee

nm

ade

toan

aly

zeA

ert

ech

'sp

rob

lem

s,m

ake

help

ful

reco

mm

end

atio

ns,

and

urg

eth

emto

fab

ricate

and

per

form

pre

lim

inary

testi

ng

pri

or

tore

ceip

to

fm

ult

ipli

ers

fro

mA

pp

lied

Res

earc

h,

Inc.

Oth

erp

rocu

rem

en

ts,

inclu

din

gw

aveg

uid

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mp

on

ents

fro

mW

aveC

om,

co

ole

dam

pli

fier

fro

mC

om

tech

,an

dsy

nth

esi

zers

fro

mF

luk

e,

ap

pear

tob

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wit

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nee

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83

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(Con

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143