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EECE 413, Fall, 2006
1
Prob. 3.6
bsasksD
)(
The read arm on a computer disk drive has the transfer function
Design a digital controller that has a bandwidth of 100 Hz and a phase margin of 50. Use a sample rate of 6 kHz.
Method 1: Simplest approach is single lead with 10:1 lead ratio (b/a = 10) for PM = 50. For wbw = 2*pi*100, pick a = wbw/sqrt(10) & b = wbw*sqrt(10). Then adjust k so that crossover is at max. phase. k = 1300.
2
1000)(s
sG
-20
-10
0
10
20
Mag
nitu
de (d
B)
101
102
-181
-180.5
-180
-179.5
-179
Phas
e (d
eg)
Bode DiagramGm = 0 dB (at 31.6 rad/sec) , Pm = 0 deg (at 31.6 rad/sec)
Frequency (rad/sec)
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0
50
100
Mag
nitu
de (d
B)
105
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Phas
e (d
eg)
Bode DiagramGm = Inf dB (at Inf rad/sec) , Pm = 54.9 deg (at 650 rad/sec)
Frequency (rad/sec)
% Prob_3_6.m%G = tf(1000,[1 0 0]);w = 2*pi*100;a = w/sqrt(10);b = w*sqrt(10);k = 1300;D = tf(k*[1 a],[1 b]);figure(1)subplot(2,2,[1 3])margin(G),grid onsubplot(2,2,[2 4])margin(G),grid on,hold onmargin(D*G),grid on,hold off figure(2)sysCL = feedback(D*G,1);margin(sysCL),grid on
EECE 413, Fall, 2006
2
Prob. 3.6 - cont
aeeKbuusEasKsUbsbsasK
sEsUsD ooo
)()()()()(
)1(11)(
1)(
11)1(
kebTaTKke
bTKku
bTku o
o
Starting with
Plug in an approximation for each derivative
)()1()()()1()( kaeTkekeKkbu
Tkuku
o
Or change k->k+1 & k-1->k to solve for u(k+1)
)1()(1)(1)1( keKkeaTKkubTku ooOr from eq. 3.7, the equation is:
1.3
2600013.57*650
2
TPhase decrease due to sampling is (p. 63, eqn. 3.10)
Digital PM = 54.7 – 3.1 = 51.6 degrees
[1-bT] = [1 – 1987/6000] = 0.6688a*T-1 = 198.7/6000 – 1 = -0.9667k*(a*T-1) = -1257
EECE 413, Fall, 2006
3
Prob. 3.6 - cont
101
102
103
104
105
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-45
0
Phas
e (d
eg)
Bode DiagramGm = Inf dB (at Inf rad/sec) , Pm = 109 deg (at 737 rad/sec)
Frequency (rad/sec)
-80
-60
-40
-20
0
20
Mag
nitu
de (d
B) System: sysCLFrequency (rad/sec): 1.05e+003
Magnitude (dB): -2.98
% Prob_3_6.m%G = tf(1000,[1 0 0]);w = 2*pi*100;a = w/sqrt(10);b = w*sqrt(10);k = 1300;D = tf(k*[1 a],[1 b]);figure(1)subplot(2,2,[1 3])margin(G),grid onsubplot(2,2,[2 4])margin(G),grid on,hold onmargin(D*G),grid on,hold off figure(2)sysCL = feedback(D*G,1);% [mag,phase,w] = bode(sysCL);% loglog(w,mag(:)),grid onmargin(sysCL),grid on
Bandwidth check: wbw ~ 1050 Hz = 167 rad/s @ -3dB, which is high.
EECE 413, Fall, 2006
4
Prob. 3.6 - contNote, if bandwidth is important should lower crossover frequency by factor of 1/1.67, ie., a2 = a/1.67 ~ 125 & b2 = b/1.67 = 1250. May find k=500 by iteration to get wbw ~ 630 rad/s.
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0
50
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Mag
nitu
de (d
B)
100
101
102
103
104
105
-180
-150
-120
Phas
e (d
eg)
Bode DiagramGm = Inf dB (at Inf rad/sec) , Pm = 54.9 deg (at 399 rad/sec)
Frequency (rad/sec)
% Prob_3_6.m%G = tf(1000,[1 0 0]);w = 2*pi*100;a = w/sqrt(10);b = w*sqrt(10);k = 1300;D = tf(k*[1 a],[1 b]);figure(1)figure(3)margin(D*G),grid on,hold ona = 125;b = 1250;k = 500;D = tf(k*[1 a],[1 b]);margin(D*G),grid on,hold off
EECE 413, Fall, 2006
5
Prob 3.6 – Optimization Methodfunction cf = optim_3_6(xin);% Prob_3_6 optimization%G = tf(1000,[1 0 0]);k = xin(1);a = xin(2);b = xin(3);D = tf(k*[1 a],[1 b]);[Gm,Pm,Wcg,Wcp] = margin(D*G);[mag,phase,w] = bode(D*G);i = find(mag >= 0.7);[y,i] = min(mag(i));wbw = 2*pi*100;Pm = Pm - w(i)/6000/2;cf = abs(Pm - 50) + abs(wbw - w(i))/2;[xin, cf]save 3_6_param xin
PM = 50 check: PM ~ 50.1 – 3 ~ 47Is a little low.
Lead gainsbsasksD
)(
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0
50
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Mag
nitu
de (d
B)
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102
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105
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Phas
e (d
eg)
Bode DiagramGm = Inf dB (at Inf rad/sec) , Pm = 50.1 deg (at 481 rad/sec)
k,a,b = [803.20696 222.20451 1776.6704], frequency (rad/sec)
Key points are that: 1) must start at good initialization other methods may be used for initialization, 2) needs to restart occasionally to avoid local minimums or getting stuck, 3) won’t converge for wrong structure.
EECE 413, Fall, 2006
6
Prob 3.6 – Optimization Method - cont% Prob_3_6_main_optim.m%if 0 clear * w = 2*pi*100; a = w/sqrt(10); b = w*sqrt(10); k = 1300; xin = [k,a,b]; load 3_6_param xin = fminsearch('optim_3_6',xin);endif 1 clear * load 3_6_param k = xin(1); a = xin(2); b = xin(3); D = tf(k*[1 a],[1 b]); G = tf(1000,[1 0 0]); figure(1) margin(G),grid on,hold on margin(D*G),grid on,hold off xlabel(['freq rad/s, k,a,b = ',num2str(xin)]) figure(2) sysCL = feedback(D*G,1); % [mag,phase,w] = bode(sysCL); % loglog(w,mag(:)),grid on margin(sysCL),grid onend
101
102
103
104
105
-180
-135
-90
-45
0
Phas
e (d
eg)
Bode DiagramGm = Inf dB (at Inf rad/sec) , Pm = 102 deg (at 580 rad/sec)
Frequency (rad/sec)
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-40
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0
20
System: sysCLFrequency (rad/sec): 783
Magnitude (dB): -3.02
Mag
nitu
de (d
B)
Bandwidth check: 783 > 630, a bit highAlthough, fminsearch based optimization is very fast, sometimes a number of revisits are necessary while adjusting cost function weights.
EECE 413, Fall, 2006
7
Problem 3.7 - cont2
1)(s
sG
bsask
Design feedback with lead compensation for the open-loop system:
R(t)2
1s
The rise time should be <= 1 sec & the overshoot should be <= 15% @ 5 Hz sampling rate. Do continuous 1st, then discrete. Find difference equations.
D(s) G(s)
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Mag
nitu
de (d
B)
10-2
10-1
100
101
102
103
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-150
-120
-90
Phas
e (d
eg)
Bode DiagramGm = Inf dB (at Inf rad/sec) , Pm = 75.2 deg (at 2.54 rad/sec)
Frequency (rad/sec)
% Prob_3_7.m%G = tf(1,[1 0 0]);a = 0.5;b = 40;k = 100;D = tf(k*[1 a],[1 b]);figure(1)margin(G),grid on,hold onmargin(D*G),grid on,hold offfigure(2)sysCL = feedback(D*G,1);step(sysCL,5),grid onxlabel(['time in, k,a,b = ',…num2str([k,a,b]),' time in'])
PM frequency near peak of phase plot.
D(s) found by trial & error.
EECE 413, Fall, 2006
8
Step Response
time in, k,a,b = 100 0.5 40 time in (sec)
Ampl
itude
0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 50
0.2
0.4
0.6
0.8
1
1.2
1.4
System: sysCLTime (sec): 1.52Amplitude: 1.12
System: sysCLTime (sec): 0.0644Amplitude: 0.102
System: sysCLTime (sec): 0.642Amplitude: 0.901
Problem 3.7 - cont
1010
51/2
51/2
/2/2)(
ssTsTsGh
All the specifications are met in continuous time: the rise time is <= 1 sec & the overshoot is <= 15%. Next step is sample at 5 Hz.
Design now using zero order hold approximation:
22 10101
1010)(
sssssG
With new plant model repeat design
EECE 413, Fall, 2006
9
Step Response
Time (sec)
Ampl
itude
0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 50
0.2
0.4
0.6
0.8
1
1.2
1.4System: sysCLTime (sec): 1.32Amplitude: 1.16
System: sysCLTime (sec): 0.128Amplitude: 0.103
System: sysCLTime (sec): 0.602Amplitude: 0.903
Problem 3.7 - cont
Design now using zero order hold approximation:
22 10101
1010)(
sssssG
New plant model
Slightly > 15% overshoot
% Prob_3_7.m%G = tf(1,[1 0 0]);a = 0.5;b = 40;k = 100;D = tf(k*[1 a],[1 b]);figure(1)margin(G),grid on,hold onmargin(D*G),grid on,hold off figure(2)sysCL = feedback(D*G,1);step(sysCL,5),grid onxlabel(['time in, k,a,b = ',…num2str([k,a,b]),' time in'])G = tf(10,[1 10 0 0]);figure(3)sysCL = feedback(D*G,1);step(sysCL,5),grid on
EECE 413, Fall, 2006
10
Prob 3.7 - cont
Step Response
Time (sec)
Ampl
itude
0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 50
0.2
0.4
0.6
0.8
1
1.2
1.4System: sysCLTime (sec): 1.05Amplitude: 1.14
System: sysCLTime (sec): 0.105Amplitude: 0.103
System: sysCLTime (sec): 0.502Amplitude: 0.904
% Prob_3_7.mG = tf(10,[1 10 0 0]);a = 0.5;b = 80;k = 250;D = tf(k*[1 a],[1 b]);figure(1)sysCL = feedback(D*G,1);step(sysCL,5),grid on
Overshoot now less than 15%. Gains found by trial & error.
EECE 413, Fall, 2006
11
Determine parameters to satisfy requirements. Step 1: Find new open-loop crossover frequency from desired ωn=ωmax, the point the phase lead is added.Step 2: Evaluate the PM of KG(ω) at the desired cross over frequency ωn.Step 3: Allow for some extra PM (5 to 12 degrees), and determine the needed phase lead φmax
Step 4: Compute
Step 5: Verify the design using matlab. Redo if needed.
Prob. 3.7 – lead compensator approach
505.0
8.118.18.18.1
max
PM
tt
rn
nr
1,11)(
ssKsD
2
1)(s
sG
maxmax
max 1,sin1sin1
The rise time should be <= 1 sec & the overshoot should be <= 15% @ 5 Hz sampling rate. Do continuous 1st, then discrete. Find difference equations.
Here parameters K, φmax and ωmax are to be determined from design specifications. x
1005.0 PM
EECE 413, Fall, 2006
12
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0
50
100
150
Mag
nitu
de (d
B)
10-2
10-1
100
101
102
-180
-150
-120
Phas
e (d
eg)
Bode DiagramGm = Inf dB (at Inf rad/sec) , Pm = 55 deg (at 1.77 rad/sec)
Frequency (rad/sec)
-40
-20
0
20
40
Mag
nitu
de (d
B)
10-1
100
101
-181
-180.5
-180
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-179
Pha
se (
deg)
Bode DiagramGm = 0 dB (at 1 rad/sec) , Pm = 0 deg (at 1 rad/sec)
Frequency (rad/sec)
Prob. 3.7 – lead compensator approach - cont
maxmax
max 1,sin1sin1
1.7620994.08.111
0994.0
18055sin1
18055sin1
max
From the margin plot φmax = PMdes + allowance – PM = 50+5-0 = 55
1,11)(
ssKsD
G = tf(1,[1 0 0]);figure(1)margin(G),grid on,hold onfigure(2)margin(G),grid on,hold onalph = 0.0994;tau = 1.762;k = 1;D = tf(k*[tau 1],[alph*tau 1]);margin(D*G),grid on,hold on
EECE 413, Fall, 2006
13
Prob. 3.7 – lead compensator approach - contThe rise time should be <= 1 sec & the overshoot should be <= 15% @ 5 Hz sampling rate. Overshoot is exceeded.
Step Response
k,alph,tau = 1 0.0994 1.7621 time in (sec)
Ampl
itude
0 1 2 3 4 5 6 7 8 9 100
0.2
0.4
0.6
0.8
1
1.2
1.4 System: sysCLTime (sec): 1.74Amplitude: 1.23
System: sysCLTime (sec): 0.163Amplitude: 0.106
System: sysCLTime (sec): 0.799Amplitude: 0.897
EECE 413, Fall, 2006
14
G = tf(1,[1 0 0]);figure(1)margin(G),grid on,hold onfigure(2)margin(G),grid on,hold onalph = 0.0994;w = 1.8;tau = 1/sqrt(alph)/w;k = 1;D = tf(k*[tau 1],[alph*tau 1]);margin(D*G),grid on,hold onk = 1;D = tf(k*[tau 1],[alph*tau 1]);margin(D*G),grid on,hold offfigure(3)sysCL = feedback(D*G,1);step(sysCL,10),grid on,hold onxlabel(['k,alph,tau = ',…num2str([k,alph,tau]),' time in'])G = tf(10,[1 10 0 0]);sysCL = feedback(D*G,1);step(sysCL,10),grid on,hold off
Prob. 3.7 – lead compensator approach - contThe rise time should be <= 1 sec & the overshoot should be <= 15% @ 5 Hz sampling rate. Overshoot is exceeded. This time see the effects of sampling at 5 Hz (~ 32%). For solution must iterate on lead parameters. Remember that overshoot related to damping coefficient can increase damping coefficient to reduce overshoot.
Step Response
k,alph,tau = 1 0.0994 1.7621 time in (sec)
Ampl
itude
0 1 2 3 4 5 6 7 8 9 100
0.2
0.4
0.6
0.8
1
1.2
1.4
System: sysCLTime (sec): 1.62Amplitude: 1.32
System: sysCLTime (sec): 1.72Amplitude: 1.23
22 10101
1010)(
sssssG
Digital plant approximation. Since is linear may be applied to lead or plant.
EECE 413, Fall, 2006
15
Step Response
k,alph,tau = 1 0.017332 2.5319 time in (sec)
Ampl
itude
0 1 2 3 4 5 6 7 8 9 100
0.2
0.4
0.6
0.8
1
1.2
1.4
System: sysCLTime (sec): 1.72Amplitude: 1.12
System: sysCLTime (sec): 1.29Amplitude: 1.14
Prob. 3.7 – lead compensator approach - contThe rise time should be <= 1 sec & the overshoot should be <= 15% @ 5 Hz sampling rate. Specs are now met at 5 Hz.
figure(4)alph = (1-sin(75*pi/180))/(1+sin(75*pi/180));w = 3;tau = 1/sqrt(alph)/w;k = 1;D = tf(k*[tau 1],[alph*tau 1]);G = tf(1,[1 0 0]);sysCL = feedback(D*G,1);step(sysCL,10),grid on,hold onxlabel(['k,alph,tau = ',…num2str([k,alph,tau]),' time in'])G = tf(10,[1 10 0 0]);sysCL = feedback(D*G,1);step(sysCL,10),grid on,hold off
5 Hz sampling rate
continuous
EECE 413, Fall, 2006
16
Approximate Analysis of Sampling Effect
Example 3.2: Check using sample rates of 20 Hz & 40 Hz. 10
270)(,1
1)(
sssD
sssG
sys1 = tf(70*[1 2],[1 10]);sysCL = feedback(sys1,1);damp(sysCL)T = 1/20;sys2 = tf(2/T,[1 2/T])*sys1;sysCL = feedback(sys2,1);damp(sysCL)
‘damp’ generates eigenvalues & damping coefficients. PM ~ 100*ζ, therefore the PM may be estimated from ‘damp’. Also, ζ is related to overshoot as discussed before. We may determine how close digital performance is to continuous.
Eigenvalue Damping Freq. (rad/s) -2.11e+000 1.00e+000 2.11e+000 Eigenvalue Damping Freq. (rad/s) -2.11e+000 1.00e+000 2.11e+000 -2.85e+003 1.00e+000 2.85e+003
outputs
EECE 413, Fall, 2006
17
Controller Tuning Guides
100100
PMPM
bsasksD
)(
nrt
8.1
nst
6.4
10,21 eM p
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 10
10
20
30
40
50
60
70
80
90
100
Mp,
%
Relation of overshoot to ζ.
Relation of settling time to ζ & ωn.
Relation of rise time to ωn.
Relation of phase margin to ζ.
maxmax
max 1,sin1sin1
1,11)(
ssKsD
10,10 bwbw ba
Adjust k so that ωmax is at crossover Adjust k so that ωbw is at crossover.
Use the above relationships to adjust the parameters below. If bandwidth is off, adjust ωmax or ωbw accordingly below. If settling time or rise time excessive increase ωmax or ωbw or PM. Note, that PM may be increased by changing from 10 to a larger number below.
EECE 413, Fall, 2006
18
Another max phase lead method
290tan
290tan
tan290
max2
max1
1max
ba
ba
ba
abba
max
1max tan290
6224)(
ssssG
Lead compensation is used to:1. Increase gain2. Increase phase margin3. Increase bandwidth
Lead exists when a < b.
Governing equationsLead compensator
bsasksD
)(
Get lead ratio from governing equation.
Example: Design lead to produce PM = 45 & tr < 1 sec
-150
-100
-50
0
50
100
Mag
nitu
de (d
B)
10-2
10-1
100
101
102
103
-270
-225
-180
-135
-90
Phas
e (d
eg)
Bode DiagramGm = 12 dB (at 3.46 rad/sec) , Pm = 38.1 deg (at 1.54 rad/sec)
Frequency (rad/sec)
G = zpk([],[0 -2 -6],24);margin(G)
Note: PM = 38 < 45 + 5 & wn = 1.54 < 1.8*1;Must increase PM & wn φmax = 50 – 38 = 12
6558.039tan21290tan
290tan 22max2
ba
nrt
8.1
EECE 413, Fall, 2006
19
Lead example - cont
6558.0ba
2max b
baab
φmax = 12
Since wn > 1.8 to meet tr, try wmax = 2.145.1746.1*6558.0,746.1
6558.02
6558.02 22max
ab
bbba
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0
50
100
Mag
nitu
de (d
B)
10-2
10-1
100
101
102
103
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-180
-90
0
90
Phas
e (d
eg)
Bode DiagramGm = 15.2 dB (at 4.04 rad/sec) , Pm = 56.6 deg (at 1.3 rad/sec)
Frequency (rad/sec)
G = zpk([],[0 -2 -6],24);a = 1.145;b = 1.746;k = 1;D = tf([1 a],[1 b]);figure(2)margin(G),hold onmargin(D),hold onmargin(D*G),hold off
PM OK, but tr/bandwidth too low, so increase k.
EECE 413, Fall, 2006
20
Lead example - cont
Step Response
Time (sec)
Ampl
itude
0 1 2 3 4 5 6 70
0.2
0.4
0.6
0.8
1
1.2
1.4
System: untitled2Time (sec): 1.15Amplitude: 0.906
System: untitled2Time (sec): 0.353Amplitude: 0.106
System: untitled1Time (sec): 1.32Amplitude: 0.907
Rise time check: increase gain makes tr very close & it may be close enough.
k = 1
k = 1.2;D1 = tf(k*[1 a],[1 b]);step(feedback(D*G,1)),hold onstep(feedback(D1*G,1)),hold off
k = 1.2
EECE 413, Fall, 2006
21
PID Control Discretization
)()(
)()(
)()(
0
teKTtu
deTKtu
tKetu
d
t
i
)1()()(
)()1()(
)()(
kekeTKTku
kTeTKkuku
kKeku
d
i
eTeT
eKu
sTsT
KsesusD
di
di
1
11)()()(
)2()1(21)(1)1()( ke
TTke
TTke
TT
TTKkuku ddd
i
continuous discrete
ProportionalIntegralderivative
Combined transfer function
Using Euler’s method we have:
EECE 413, Fall, 2006
22
Chapter 3 Summary
Tkxkxkx )()1()(
TsTsGh/2/2)(
2T
Euler approximation for derivative
Digitization permits designer to convert continuous equations to a programmable form.
If sampling rate => 30xbandwidth the digital system approximates continuous. Therefore, continuous analyses will be applicable.
If sampling rate [10 – 30]xbandwidth the digital system deviates from continuous. Therefore, approximations are needed in this bandwidth. A 1st order analysis may be used by introducing a delay of T/2 into the system. The zero-pole linear transfer function Gh(s) is an approximation of a T/2 delay.
The effects of sampling rate may be more accurately analyzed in the frequency response where the phase may be decreased by the equation.
sT
sTK
sesusD d
i
11)()()( A continuous PID transfer function
)2()1(21)(1)1()( ke
TTke
TTke
TT
TTKkuku ddd
i
A digital PID transfer function implementation
For digital control systems with sampling rates < 30xbandwidth the design is often carried out in the discrete domain, eliminating approximation errors.
EECE 413, Fall, 2006
23
Discrete StabilityDiscrete stability requires that the closed-loop system characteristic equation roots be in the unit circle, i.e.., they be < 1.
Examples: check for stability
u(k) = 0.9u(k-1) – 0.2u(k-2) is the characteristic equation, let u(k) = zk
zk = 0.9zk-1 – 0.2zk-2 then multiply by z-k
1 = 0.9z-1 – 0.2z-2 then multiply by z2
z2 = 0.9z – 0.2 z2 – 0.9z + 0.2 = 0 is the characteristic equation.roots([1 -0.9 0.2]) ans = [ 0.5000 0.4000] stable
u(k) = 0.5u(k-1) – 0.3u(k-2) is the characteristic equation, let u(k) = zk
zk = 0.5zk-1 – 0.3zk-2 then multiply by z-k
1 = 0.5z-1 – 0.3z-2 then multiply by z2
z2 = 0.5z – 0.3 z2 – 0.5z + 0.3 = 0 is the characteristic equation.roots([1 -0.5 0.3]) ans = [ 0.2500 + 0.4873i, 0.2500 - 0.4873i]abs(roots([1 -0.5 0.3])) ans = [ 0.5477 0.5477] stable
u(k) = 1.6u(k-1) – u(k-2) is the characteristic equation, let u(k) = zk
zk = 1.6zk-1 – zk-2 then multiply by z-k
1 = 1.6z-1 – z-2 then multiply by z2
z2 = 1.6z – 1 z2 – 1.6z + 1 = 0 is the characteristic equation.roots([1 -1.6 1]) ans = [ 0.8000 + 0.6000i, 0.8000 - 0.6000i]abs(roots([1 -1.6 1])) ans = [ 1.0000 1.0000] unstable
u(k) = 0.8u(k-1) + 0.4u(k-2) is the characteristic equation, let u(k) = zk
zk = 0.8zk-1 + 0.4zk-2 then multiply by z-k
1 = 0.8z-1 + 0.4z-2 then multiply by z2
z2 = 0.8z + 0.4 z2 – 0.8z - 0.4 = 0 is the characteristic equation.roots([1 -0.8 -0.4]) ans = [1.1483 -0.3483]] unstable
EECE 413, Fall, 2006
24
Discrete StabilityDiscrete stability requires that the closed-loop system characteristic equation roots be in the unit circle, i.e.., they be < 1.
Problem 4.8Use matlab to determine how many roots of the following are outside the unit circle.(a) z2 + 0.25 = 0(b) z3 – 1.1z2 + 0.01z + 0.405 = 0(c) z3 – 3.6z2 + 4z – 1.6 = 0
(a) pa = [1 0 0.25];abs(roots(pa))ans = [0.5000 0.5000]All roots are inside the unit circle(b) pb = [1 -1.1 .01 .405];abs(roots(pb))ans = [0.9 0.9 0.5]All roots are inside the unit circle(c) pc = [1 -3.6 4 -1.6];abs(roots(pc))ans = [2 0.8944 0.8944]One root is outside the unit circle
EECE 413, Fall, 2006
25
Discrete Example4.6 Show that the characteristic equation z2 – 2r cos(θ)z + r2 has the roots z1,2 = rexp(+_jθ)
Roots = [2r cos(θ) +- sqrt[(2r cos(θ))* (2r cos(θ)) – 4r2]]/2] = r cos(θ) +- r sqrt(cos2(θ) – 1)= r cos(θ) +- r sqrt(sin2(θ))= r cos(θ) +- jr sin(θ) = r (cos(θ) +- j sin(θ)) = rexp(+_jθ)
Block Diagrams
Parallel blocks
H1(z)
H2(z)
H(z) = H1(z) + H2(z)
H1(z) H2(z)Series blocks H(z) = H1(z) * H2(z)
H1(z)
H2(z)
Feedback TransferFunction
H(z) = H1(z) / [1 - H1(z) H2(z)]
H1(z) H2(z) H(z) = H1(z)H2(z) / [1 - H1(z) H2(z)]
EECE 413, Fall, 2006
26
Block Diagrams
11
2112
)()()(
)(112
)(
)(
1
1
1
1
zzT
zzTzH
zEzU
zEzzTzU
zuzUk
kk
nn
mm
zazazazbzbbzH
2
21
1
110
1)(
)()()( 2
21
1
110
zazb
azazazzbzbzbzH
nnnn
mnm
nn
Recurrence or difference equation:uk = -a1uk-1 – a2uk-2 - … - anuk-n + b0ek + b1ek-1 + … bmek-m
Taking the z-transform we have:
If n>m we can write:
11 2 kkkk eeTuu
Trapezoidal rule
Z-1 T/2
Z-1
ek ek-1
uk
uk-1
Trapezoidal rule block diagram
EECE 413, Fall, 2006
27
Canonical Forms & Block Diagrams
)()(,)()(
,)()()()()()()(
zEzazazE
zbzEzazbzEzHzU
)(12)(3,
,
321
322
13
322
13
kakakakekazazaez
azazaze
2k
Control canonical formIn the 3rd order case below u, e, & ζ are time variables and z is an advance operator.
Z-1 1k 3k
Z-1 Z-1
k
33 kz
Delay operators
Step 1: create state variables from above equation(s)
See figure 4.8 b & c, p. 86, for completion. In these figures the internal variables are x1, x2, & x3. These variables comprise the state of the system. Note that they are related: x3(k+1) = x2(k), etc. The sum at the far left of the figure is:
)()1()()1(
)()()()()1(
)()()()()1(
23
12
3322111
3322111
kxkxkxkx
kekxakxakxakx
kekxakxakxakx
EECE 413, Fall, 2006
28
Vector Matrix Notation for Control Canonical Form
)()1()()1(
)()()()()1(
23
12
3322111
kxkxkxkx
kekxakxakxakx
)()()1( keBkxAkx cc
001
,010001,321
3
2
1
cc Baaa
Axxx
x
State equations Vector-Matrix form
where
The output equation is:
ebxbabxbabxbabu 0303320221011 )()()( Vector-Matrix form
eDxCu cc
0
033022011 ,bD
babbabbabC
c
c
where
Observer canonical form
ebzebezbezbuazuauzauz 322
13
0322
13 Note that e(k) is the external input and u(k) is the output.
We rewrite the above as
zebezbezbuazuauzauzuaeb 22
13
0322
13
33 This is used to build the block diagrams of figure 4.9 on p. 88.
EECE 413, Fall, 2006
29
Observer Canonical Form
0
303
202
101
3
2
1
001
001001
)()()()()()1(
bDC
abbabbabb
B
aaa
A
keDkxCkukeBkxAkx
o
o
o
o
oo
oo
8.06.1
25.05.018.04.26.225.025.05.0
22
2
234
23
zzzzzzz
zzzzzzzzH
Constructing the Vector-Matrix form we have:
Control & observer canonical forms are ‘direct’ canonical forms because the gains of the realizations are coefficients in the block diagrams.
A very useful form is the cascade canonical form which is constructed by placing multiple 1st or 2nd order transfer functions in series. See the following example.
zzz2
181.06.125.05.0
2
2
zzzze(k) u(k)
EECE 413, Fall, 2006
30
Discrete Models of Sampled Data Systems
ssGe Ts )(1
ssGeZ
ssGZ
ssGeZzG TsTs )()()(1)(
D/A G(s) A/Du(kT) y(t) y(kT)
The unit impulse response of a plant is:
Taking the z-transform we have:
Since the exponential term is exactly the delay of one period we have:
ssGZz
ssGZezG Ts )(1)(1)( 1
The D/A converter shown above is called a zero-order hold (ZOH). It accepts a sample at t = kT & holds its output constant at this value until the next sample is sent at t = kT + T. The output of the D/A is applied to the plant.
Which is the unit impulse transfer function of a ZOH.
EECE 413, Fall, 2006
31
ZOH examples
ssGZzzG )(1)( 1
assassa
ssG
11)(
aT
aT
aT ezzez
ezz
zz
ssGZ
11
1)(
What is the discrete transfer function of G(s) = a/(s+a) preceded by a ZOH?
Using table look-ups we have:
aT
aT
aT
aT
aT
aT
eze
ezzez
zz
ezzezzzG
1
111
111)( 1
ssGZzzG )(1)( 1
3
1)(ss
sG
3
2
11
2)(
zzzT
ssGZ
What is the discrete transfer function of G(s) = 1/s/s preceded by a ZOH?
Using table look-ups we have:
2
2
3
21
11
211
21)(1)(
zzT
zzzT
zz
ssGZzzG
EECE 413, Fall, 2006
32
ZOH examples
2115.0)(
zzzG
ssGZ
zzzG l
)(1)( 1 asasH
)(
ssGZzzG )(1)( 1 3
1)(ss
sG
What is the discrete transfer function of G(s) = 1/s/s preceded by a ZOH, using the sample period T = 1?
T = 1;numC = 1;denC = [1 0 0];sysc = tf(numC,denC);sysd = c2d(sysc,T);[numd,dend,T] = tfdata(sysd);
numd = [0 0.5 0.5], dend = [1 -2 1]G(z) =
0.5 z + 0.5----------------z^2 - 2 z + 1
ssGZzzG )(1)( 1
ssHee
ssHe
ssGsHesG
mTslTs
smTlTs )()()(),()(
What is the discrete transfer function of G(s) = 1/s/s preceded by a ZOH, using the sample period T = 1?
λ = lT-mT and l, m are integers. If
amT
amT
l
mTsmTs
l ezze
zz
zzz
ase
seZ
zzzG
1111)( 1
EECE 413, Fall, 2006
33
ZOH Examples
amT
amT
l
mTsmTs
l ezze
zz
zzz
ase
seZ
zzzG
1111)( 1
amT
aTamT
aTlamT
eee
ezzzezG
1
1)(
aT
amTaT
l ezzezezz
zzzG
111)(
Zero position
For a = 1, T = 1, & λ = 1.5, we have: l = 2 & m = 0.5 & 3679.06025.0)( 2
zzzzG
Td = 1.5; a = 1; T = 1;Sysc = tf(a,[1 a],’td’,Td);Sysd = c2d(Sysc,T);
Matlab code that generates the transfer functions:
G(s) = 1exp(-1.5*s) * ----- s + 1
G(z) =
0.3935 z + 0.2387z^(-1) * ----------------------- z^2 - 0.3679 z
EECE 413, Fall, 2006
34
ZOH Examples – 4.9 h
sK
313,1,,1,
313,
33,
5.1
22
2/
2
sse
ss
se
ss
sssssK TssT
Compute using matlab the discrete transfer function for the sampling period T = [0.05,0.5], if the G(s) is:
T = 0.05 G(z) = 0.05K -------- z - 1
ssGZzzG )(1)( 1
D/A G(s) A/Du(kT) y(t) y(kT)
T = 0.5 G(z) = 0.5K -------- z - 1
33ss
T = 0.05 G(z) = 0.003569 z + 0.003395 ------------------------------ z^2 - 1.861 z + 0.8607
T = 0.5 G(z) = 0.241 z + 0.1474 ------------------------z^2 - 1.223 z + 0.2231
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y A
xis
0 5 10 150
0.01
0.02
0.03
0.04
0.05
0.06Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
2
4
6
8
10
12
14
16Step Response
Time (sec)
Ampl
itude
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 150
0.05
0.1
0.15
0.2
0.25
0.3
0.35
0.4
0.45
0.5Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
5
10
15Step Response
Time (sec)
Ampl
itude
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 150
0.01
0.02
0.03
0.04
0.05
0.06Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
5
10
15Step Response
Time (sec)
Ampl
itude
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y A
xis
0 5 10 150
0.1
0.2
0.3
0.4
0.5
0.6
0.7Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
5
10
15Step Response
Time (sec)
Ampl
itude
EECE 413, Fall, 2006
35
T = 0.05 G(z) = 0.00125 z + 0.00125 --------------------------- z^2 - 2 z + 1
T = 0.5 G(z) = 0.125 z + 0.125 ---------------------- z^2 - 2 z + 1
2
2/
sesT
ZOH Examples – 4.9 h
313 ss
2
1ss
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y A
xis
0 5 10 150
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
20
40
60
80
100
120Step Response
Time (sec)
Am
plitu
de
T = 0.05 G(z) = 0.00351 z + 0.003284 ------------------------------ z^2 - 1.812 z + 0.8187
T = 0.5 G(z) = 0.2018 z + 0.1039-------------------------------z^2 - 0.8297 z + 0.1353
T = 0.05 G(z) = 0.05125 z - 0.04875 --------------------------- z^2 - 2 z + 1
T = 0.5 G(z) = 0.625 z - 0.375 ---------------------- z^2 - 2 z + 1
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 150
0.005
0.01
0.015
0.02
0.025
0.03Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1Step Response
Time (sec)
Ampl
itude
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 150
0.05
0.1
0.15
0.2
0.25
0.3
0.35Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1Step Response
Time (sec)
Ampl
itude
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 150
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
20
40
60
80
100
120
140Step Response
Time (sec)Am
plitu
de
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 150
1
2
3
4
5
6
7
8Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
20
40
60
80
100
120
140Step Response
Time (sec)
Ampl
itude
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real AxisIm
agin
ary
Axi
s0 5 10 15
0
1
2
3
4
5
6
7
8Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
20
40
60
80
100
120Step Response
Time (sec)
Ampl
itude
EECE 413, Fall, 2006
36
ZOH Examples – 4.9 h
313 5.1
sse Ts
2
1ss
T = 0.05 G(z) = -0.04875 z + 0.05125 ---------------------------- z^2 - 2 z + 1
T = 0.5 G(z) = 0.2018 z + 0.1039 -------------------------
z^2 - 2 z + 1
T = 0.05 G(z) = 0.00351 z + 0.003284 ---------------------------- z^2 - 1.812 z + 0.8187
T = 0.5 G(z) = 0.2018 z + 0.1039------ ----------------------
z^2 - 0.8297 z + 0.1353
-2 0 2-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y A
xis
0 5 10 15-0.1
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7Impulse Response
Time (sec)
Ampl
itude
0 5 10 15-20
0
20
40
60
80
100Step Response
Time (sec)
Ampl
itude
-2 0 2-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 15-1
0
1
2
3
4
5
6
7Impulse Response
Time (sec)
Ampl
itude
0 5 10 15-20
0
20
40
60
80
100Step Response
Time (sec)
Ampl
itude
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 150
0.005
0.01
0.015
0.02
0.025
0.03Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1Step Response
Time (sec)
Ampl
itude
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 150
0.05
0.1
0.15
0.2
0.25
0.3
0.35Impulse Response
Time (sec)
Ampl
itude
0 5 10 150
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1Step Response
Time (sec)
Ampl
itude
EECE 413, Fall, 2006
37
ZOH Examples – 4.9 h% Prob_4_9h.m%clear *i = 14;if i == 1,num = 1;den = [1 0];T = 0.05;endif i == 2,num = 1;den = [1 0];T = 0.5;endif i == 3,num = 3;den = [1 3 0];T = 0.05;endif i == 4,num = 3;den = [1 3 0];T = 0.5;endif i == 5,num = 3;den = [1 4 3];T = 0.05;endif i == 6,num = 3;den = [1 4 3];T = 0.5;endif i == 7,num = [1 1];den = [1 0 0];T = 0.05;endif i == 8,num = [1 1];den = [1 0 0];T = 0.5;endif i == 9,num = 1;den = [1 0 0];T = 0.05;sys = tf(num,den,'InputDelay',T/2);sysd = c2d(sys,T);endif i == 10,num = 1;den = [1 0 0];T = 0.5;sys = tf(num,den,'InputDelay',T/2);sysd = c2d(sys,T);endif i == 11,num = [-1 1];den = [1 0 0];T = 0.05;endif i == 12,num = [-1 1];den = [1 0 0];T = 0.5;endif i == 13,num = 3;den = [1 4 3];T = 0.05;sys = tf(num,den,'InputDelay',1.5*T);sysd = c2d(sys,T);endif i == 14,num = 3;den = [1 4 3];T = 0.5;sys = tf(num,den,'InputDelay',1.5*T);sysd = c2d(sys,T);endif i~=(9|10|13|14),[numd,dend] = tfc2tfd(num,den,T);sysd = tf(numd,dend,T),endfigure(1)subplot(131)pzmap(sysd)subplot(132)impulse(sysd,'*:',0:T:15)subplot(133)step(sysd,'*:',0:T:15)
Matlab code:Note that 9, 10, 13, & 14 handle transport delays in addition to the sampling intervals. All the rest deal only with sampling intervals.
eig(sys) may be used to calculate the system poles.
EECE 413, Fall, 2006
38
Discrete Models of State Space Systems
JuHxywGGuFxx
1
)()()()()1( 1
kHxykwkukxkx
NFTI
NFTFTIFTI
TGTGkTFGde
FTTFTFFTIe
k
kkTF
FT
132
!1
!3!2
00
3322
D/A F,G,H A/Du(kT) y(t) y(kT)
1
)()(
);()(
),()(
zIHzUzY
zHXzY
zUzXzI
Z-transform gives us (with w = 0):
Example Φ & Γ calculation.
NFTI
NFTFTIFTI
TGFT
132
01,10
,0010
HGF
T
TT
TTG
TTTFTI
TTTFFTI
210
102
1
101
102
10010
1001
102
1200
101001
!3!2
2
22
Sysc = ss(F,G,H,J);Sysd = c2d(Sysc,T);[phi,gam,h,J] = ssdata(Sysd);
EECE 413, Fall, 2006
39
Algorithm for State Space Discretization
TGFTI
endkFTI
kforIInitialize
,
11:1_,
)()()(),()()1(
,
,,,,,,,,,,,,
),(),,(
0000
0000
kJukHxkykukxkx
thenJuHxyGuFxx
whereuxhJuxhHuxfGuxfF
uxhyuxfx
ux
ux
Sysc = ss(F,G,H,J);Sysd = c2d(Sysc,T);[phi,gam,h,J] = ssdata(Sysd);
System poles & zerosSystem poles may be obtained from lam = eig(phi). System zeros (transmission zeros) may be computed by zer = tzeros(sysD).
Nonlinear ModelsMost systems are nonlinear. To use the linear techniques one must linearize the models by partial differentiation as shown below. For a system described below we have:
uhh
xhh
uff
xff
ux
ux
,,,
,,,,
EECE 413, Fall, 2006
40
Dynamic Response7.0z
z
45,7.0,cos2cos
22
r
rzrzrzz
1zz
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y A
xis
0 5 100
0.2
0.4
0.6
0.8
1
1.2
1.4
1.6
1.8
2Impulse Response
Time (sec)
Am
plitu
de
0 5 101
2
3
4
5
6
7
8
9
10
11Step Response
Time (sec)
Am
plitu
de
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 100
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1Impulse Response
Time (sec)
Ampl
itude
0 5 101
1.5
2
2.5
3
3.5Step Response
Time (sec)
Ampl
itude
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 15-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Impulse Response
Time (sec)
Ampl
itude
0 5 10 150.8
0.9
1
1.1
1.2
1.3
1.4
1.5Step Response
Time (sec)
Ampl
itude
45,98.0,cos2cos
22
r
rzrzrzz
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 15-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Impulse Response
Time (sec)
Ampl
itude
0 5 10 15-1
-0.5
0
0.5
1
1.5
2Step Response
Time (sec)
Ampl
itude
0,8.0,cos2cos
22
r
rzrzrzz
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y A
xis
0 5 10 150
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1Impulse Response
Time (sec)
Ampl
itude
0 5 10 151
1.5
2
2.5
3
3.5
4
4.5
5Step Response
Time (sec)
Ampl
itude
T = 0.5;for i = 1:5 if i==1,sysd = tf([1 0],[1 -1],T);end if i==2,sysd = tf([1 0],[1 -0.7],T);end if i==3, r=0.7;th=pi/180*45; sysd=tf([1 -r*cos(th) 0],[1 -2*r*cos(th) r*r],T); end if i==4, r=0.98;th=pi/180*45; sysd=tf([1 -r*cos(th) 0],[1 -2*r*cos(th) r*r],T); end if i==5, r=0.8;th=pi/180*0; sysd=tf([1 -r*cos(th) 0],[1 -2*r*cos(th) r*r],T); end figure(i) subplot(131) pzmap(sysd) subplot(132) impulse(sysd,'*:',0:T:15) subplot(133) step(sysd,'*:',0:T:15)end
EECE 413, Fall, 2006
41
Dynamic Response
180,8.0,cos2cos
22
r
rzrzrzz
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y A
xis
0 5 10 15-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Impulse Response
Time (sec)
Am
plitu
de
0 5 10 150.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1Step Response
Time (sec)
Ampl
itude
90,8.0,cos2cos
22
r
rzrzrzz
135,8.0,
cos2cos
22
r
rzrzrzz
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real AxisIm
agin
ary
Axi
s
0 5 10 15-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Impulse Response
Time (sec)
Am
plitu
de
0 5 10 15
0.4
0.5
0.6
0.7
0.8
0.9
1Step Response
Time (sec)
Am
plitu
de
-1 0 1-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Pole-Zero Map
Real Axis
Imag
inar
y Ax
is
0 5 10 15-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1Impulse Response
Time (sec)
Ampl
itude
0 5 10 15
0.4
0.5
0.6
0.7
0.8
0.9
1Step Response
Time (sec)
Ampl
itude
if i==6, r=0.8;th=pi/180*180; sysd=tf([1 -r*cos(th) 0],[1 -2*r*cos(th) r*r],T); end if i==7, r=0.8;th=pi/180*90; sysd=tf([1 -r*cos(th) 0],[1 -2*r*cos(th) r*r],T); end if i==8, r=0.8;th=pi/180*135; sysd=tf([1 -r*cos(th) 0],[1 -2*r*cos(th) r*r],T); end
EECE 413, Fall, 2006
42
-1 -0.8 -0.6 -0.4 -0.2 0 0.2 0.4 0.6 0.8 10
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0.9/T
0.8/T
0.7/T
0.6/T0.5/T
0.4/T
0.3/T
0.2/T
0.1/T
Time Domain Link
jbasjs nn
21
bTT
eer
whererez
n
aTT
j
n
21
,
,
s-planez-plane
Θ - Normalized signal frequency in radians/secondaxis([-1 1 0 1]),zgrid('new')
EECE 413, Fall, 2006
43
Prob 4.19For a 2nd order system with damping ratio 0.5 and poles at an angle in the z-plane of 30 degrees,
what % overshoot to a step would you expect if the system had a zero at z2 = 0.6?
bTT
eer
whererez
n
aTT
j
n
21
,
,
2
2
1
,cos6.0
6.0cos
T
eer
r
rz
n
aTTn