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1 Designing Pilot-Symbol-Assisted Modulation (PSAM) Schemes for Time- Varying Fading Channels...
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Transcript of 1 Designing Pilot-Symbol-Assisted Modulation (PSAM) Schemes for Time- Varying Fading Channels...
![Page 1: 1 Designing Pilot-Symbol-Assisted Modulation (PSAM) Schemes for Time- Varying Fading Channels Tharaka Lamahewa Research School of Information Sciences.](https://reader037.fdocuments.in/reader037/viewer/2022110323/56649d7f5503460f94a62320/html5/thumbnails/1.jpg)
1
Designing Pilot-Symbol-Assisted Modulation (PSAM) Schemes for Time-
Varying Fading Channels
Tharaka Lamahewa
Research School of Information Sciences and Engineering
ANU College of Engineering and Computer Science
The Australian National University (ANU)
Collaborators: Dr. Parastoo Sadeghi (ANU), Prof. Rod Kennedy (ANU), Prof. Predrag Rapajic (University of Greenwich, UK), Mr. Sean Zhou (ANU),
Dr. Salman Durrani (ANU)
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Outline
Introduction Background and Motivation
Contributions Optimum design of PSAM schemes in time-
varying fading channels Optimum design under spatially correlated
antenna arrays Conclusions
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System Modely = g x` +n`
Fading Input Noise
Received Signal:
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Adaptive Power Allocation (1)• Aim: To save the overall transmitter power by adapting the power
depending on the fading channel quality
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Adaptive Power Allocation (2)• Early studies: Perfect (Genie aided) channel state information
(CSI) at Rx and possibly delayed CSI at Tx
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Genie Aided Power Allocation Strategy• Solution: Waterfill in time, with water level 0 (Goldsmith and
Varaiya 1997)
Ed(½) =1½0
¡1½; ½ ½0
Ed(½) = 0; ½<½0
½= jgj2
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Adaptive Power Allocation (3)
Noise
Variance:
• Later studies: A vicious genie provides imperfect CSI at Rx and (possibly delayed) imperfect CSI at Tx
• The channel is measured using a probe signal continuously
Good GenieBad Genie
g = g +~g
¾2~g( )
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Power Allocation Strategy under Imperfect Channel State Information
• It is still a waterfilling strategy in time (with a more complex solution), with some water level 0 (Klein and Gallager 01, Yoo and Goldsmith 04 & 06)
½= jgj2
Ed(½) = f (½;½0;¾2~g); ½ ½0Ed(½) = 0; ½<½0
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Our Model-Based Power Adaptation with Periodic Feedback
• There is no genie
• Channel estimate is based on pilot symbol transmission
• reduction in available resources
• possible tradeoffs.
• Channel estimates are fed back after some delay.
Pilot Symbols Data Symbols
Block Length = T
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First Step
Let us consider the case where there is no feedback, for comparison purposes, and optimize pilot transmission parameters
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System Model without Feedback (1)
Pilot symbols are transmitted periodically for channel estimation
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System Model without Feedback (2)
State equation: g =®g ¡ 1+w`
First-order AR or Gauss-Markov channel model:
n` » NC (0;N0)
g » NC (0;¾2g)Observation equation:
fading
y = g x` +n`
inputnoise
small fast channellarge slow channel
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Three Parameters for Optimization How often (pilot spacing)?
How strong (pilot symbol power)?
How many (pilot cluster size)? One1
P1 D2 D3 …... DT-1 DT
´ =1T;
1. M. Dong, L. Tong, and B. M. Sadler, “Optimal insertion of pilot symbols for transmissions over time-varying flat fading channels,” IEEE Trans. Signal Processing, vol. 52, no. 5, pp. 1403–1418, May 2004.
Ep =°´E;
Ed =1¡ °1¡ ´
E
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Our Objective Function: A Capacity Lower Bound
A closed-form expression for the information capacity of the time-varying Gauss-Markov fading channel in the presence of imperfect channel estimation is still unavailable.
We utilize a lower bound to the channel capacity
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Our Objective Function: A Capacity Lower Bound1
1. M. Medard, “The effect upon channel capacity in wireless communications of perfect and imperfect knowledge of the channel,” IEEE Trans. Inform. Theory, vol. 46, no. 3, pp. 933–946, May 2000.
Note the presence of signal power in the denominator
C(g) ¸ CLB (g) = log³1+
jgj2Ed¾2~gEd+N0
´
Channel estimation: g= g+~g
estimate error
y = g x` +~g x` +n`
useful part additional noise
effective instantaneous SNR
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Average Capacity Lower Bound
• The lower bound is an average capacity per symbol and not per transmission block
• The lower bound, by itself, does not take into account models of channel time variations
• The lower bound, by itself, does not tell us how to optimize the two pilot parameters and
CLB =Egnlog³1+ jgj2Ed
¾2~gEd+N0
´o
expectations over channel estimate realizations
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First Contribution (no Feedback Yet)
Invoke the autoregressive (AR) or Gauss-Markov channel model and Kalman filtering principles to maximize the capacity lower bound
Analyse optimum pilot scheme parameters pilot power γ and pilot spacing T
to maximise the capacity lower bound for a wide range of SNR and normalized fading rates
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Estimation errorincreases
Kalman Filtering
P1 D2 D3 …... DT-1 DT
M(1) =¾2~g(1)
g1;~g1
Estimate (true filtering)
Predict (no pilots)
g = ®¡ 1g1
M ( ) =¾2~g( ) =¾2g ¡ ®2(`¡ 1)(¾2g ¡ M (1))
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Revisit the Capacity Lower Bound
P1 D2 D3 …... DT-1 DT
SNR decreases
g = ®¡ 1g1®<1
½inst( ) =jg j2Ed
¾2~g( )Ed+N0
y = g x` +~g x` +n`
signal noise
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Revisit the Lower Bound (cnt’d)
P1 D2 D3 …... DT-1 DT
Capacity per symboldecreases
Instantaneous capacity per symbol:
Instantaneous capacity per block:
CLB (½1) =1T
TX
`=2
CLB ( ;½1)
CLB ( ;½inst) = log¡1+½inst( )
¢
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LB versus Pilot Power and Spacing
Average
SNR = 10 dB
®= J 0¡2¼fD Ts
¢, fD Ts =0:1
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Equal Power Comparison
Pilot spacing is optimized
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Sensitivity of LB to Power Ratio
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Sensitivity of LB to Pilot Spacing
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Power Adaptation Based on Periodic Feedback
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System Model with Feedback
Switching period: T
• This model is still idealistic in the sense that the feedback link is noiseless.
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A Closer Look at the Transmitter ½ = jg j2
Ed(½) = f (½;½0;¾2~g` );
Ed(½) = 0;
Zero-delay power control: actual power allocation at time is performed based on the channel estimate g` = ®`¡ 1 g1
`
g` = ®`¡ 1 g1
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Transmission Block Structure
P1 D2 D3 …... Dd …. DT-1 DT
Feedback
Transmitted
Fixed Power Strategy
Adaptive Power Strategy
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Power Distribution
P1 D2 D3 …... Dd …. DT-1 DT
Total Power: Adaptive Power per Symbol
Ed(½1; ) = f (½;¾2~g` ;¢¢¢)
TX
`=d+1
E ½1
nEd(½1; )
o= (1¡ °)
(T ¡ d)TT ¡ 1
E
Ed = (1¡ °)(d¡ 1) £ T
T ¡ 1E
Ep = °E £ T
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Capacity Lower Bound per Block
P1 D2 D3 …... Dd …. DT-1 DT
Fixed Power Capacity Adaptive Power Capacity
1T
TX
`=d+1
log
Ã
1+®2(`¡ 1)½1Ed(½1; )¾2~g`Ed(½1; ) +N0
!
1T
dX
`=2
log
Ã
1+®2(`¡ 1)½1Ed¾2~g`Ed+N0
!
+CL B =
No Information
0+
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Optimization Problem Maximize the total capacity per block subject
to the power constraint in the adaptive transmission mode
maxE(`;½1)¸ 0
1T
Z (dX
`=2
logµ1+
®2(`¡ 1)½1Ed¾2~g( )Ed +N0
¶
+TX
`=d+1
logµ1+
®2(`¡ 1)½1E( ;½1)¾2~g( )E( ;½1) +N0
¶)
f (½1)d½1;
subject toTX
`=d+1
ZE( ;½1)f (½1)d½1 = (1¡ °)
(T ¡ d)(T ¡ 1)
E £ T
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Optimum Solution
A generalized water-filling algorithm
E( ;½1) =
½¡ a
c+ b
º c; ½1 > º
®2(`¡ 1) ;0; otherwise,
a = N0(2M ( ) +®2(`¡ 1)½1);
b=qº®2(`¡ 1)½1(º®2(`¡ 1)½1 +4M ( )2 +4M ( )®2(`¡ 1)½1);
c= 2M ( )(M ( ) +®2(`¡ 1)½1);
º : threshold (or associated to thewater level)
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Slow Fading
0 2 4 6 8 10 12 14 150.5
1
1.5
2
2.5
3
3.5
SNR budget, , dBOpt
imum
Cap
acity
low
er b
ound
, C
LB,
bits
/ch
use f
DT
S = 0.01
w/o feedback, data & pilot equal power
0 2 4 6 8 10 12 14 150.5
1
1.5
2
2.5
3
3.5
SNR budget, , dBOpt
imum
Cap
acity
low
er b
ound
, C
LB,
bits
/ch
use f
DT
S = 0.01
w/o feedback, data & pilot equal power
w/o feedback
0 2 4 6 8 10 12 14 150.5
1
1.5
2
2.5
3
3.5
SNR budget, , dBOpt
imum
Cap
acity
low
er b
ound
, C
LB,
bits
/ch
use f
DT
S = 0.01
w/o feedback, data & pilot equal power
w/o feedback
delay-less feedback
0 2 4 6 8 10 12 14 150.5
1
1.5
2
2.5
3
3.5
SNR budget, , dBOpt
imum
Ca
paci
ty lo
wer
bou
nd,
CLB
, bi
ts/c
h us
e fD
TS
= 0.01
w/o feedback, data & pilot equal power
w/o feedback
delay-less feedback
delay = 8
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Messages For the slow fading, even after a feedback delay of 8,
we get good SNR improvement in low SNR In high SNR, even the delay-less feedback does not
offer much compared to the case, where pilot power and spacing are optimized
However, it continues to offer improvements at high SNR, compared the equal power allocation strategy.
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Fast Fading
0 5 10 150.2
0.4
0.6
0.8
1
1.2
SNR budget, , dBOpt
imum
Cap
acity
low
er b
ound
, C
LB,
bits
/ch
use f
DT
S = 0.1
Blue: Delay 3
Pink: Without Feedback
Delay-less Feedback
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Messages Idealistically (no feedback delay), we would
get a good SNR improvement at low SNR However, with a modest delay of d = 3, the
performance rapidly drops No point in power adaptation for such a fast
fading rate Note that, we have forced the transmitter that,
in spite of feedback delay, perform power adaptation for at least one symbol
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Optimal Block Length, Slow Fading
0 5 10 15 2010
15
20
25
30
35
40
SNR budget, , dB
Opt
imim
Pilo
t sp
acin
g, T
*fDT
S = 0.01
w/o feedbackwith feedback, delay d = 0with feedback, delay d = 8
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Message In the slow fading regime, the optimal block
length without feedback is large enough to accommodate power adaptation
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39
Optimal Block Length, Fast Fading
0 5 10 15 20
3
4
5
6
7
8
9
SNR budget, , dB
Opt
imim
Pilo
t sp
acin
g, T
*fD
TS
= 0.1
w/o feedbackwith feedback, delay d = 0with feedback, delay d = 3with feedback, delay d = 8
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Message In the fast fading regime, the optimal block
length without feedback is so small that it cannot accommodate any power adaptation
Note that the optimal T* is less than half of what would have in a bandlimited fading channel according to the Nyquist rate (fDT = 0.1 Tmin=10)
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Optimal Pilot Power Allocation
0 5 10 15 200
0.2
0.4
0.6
0.8
1O
ptim
im P
ilot
pow
er r
atio
, *
SNR budget, , dB
with feedback, fD
Ts = 0.01
w/o feedback, fD
Ts = 0.01
with feedback, fD
Ts = 0.1
w/o feedback, fD
Ts = 0.1
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42
Message In the slow fading, the pilot power ratio in the
without feedback scheme, is a reasonable choice for the feedback scheme too.
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Multiple Antennas at the Receiver
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A Capacity Lower Bound: SIMO
Instantaneous capacity per symbol:
CLB ;` = E h `
nlog2
¯¯I +½d(½dM ss;`+I )
¡ 1h`hy`
¯¯¯o
½d : data symbol SNR;
h` : channel estimate;
M ss;` : steady-state channel covariancematrix
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LB vs SNR: Spatially i.i.d. Channels
0 2 4 6 8 10 12 14 16 18 200
1
2
3
4
5
6
7
8
SNR budget, , dB
CLB
in b
its p
er
tra
nsm
issi
on
fD
Ts = 0.01, N
r=8
fD
Ts = 0.01, N
r=4
fD
Ts = 0.11, N
r=8
fD
Ts = 0.11, N
r=4
Solid lines: using opt. parameters corresponding to SIMO boundDashed lines: using opt. parameters corresponding to SISO bound
![Page 46: 1 Designing Pilot-Symbol-Assisted Modulation (PSAM) Schemes for Time- Varying Fading Channels Tharaka Lamahewa Research School of Information Sciences.](https://reader037.fdocuments.in/reader037/viewer/2022110323/56649d7f5503460f94a62320/html5/thumbnails/46.jpg)
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LB vs SNR: Spatially Correlated Channels
0 2 4 6 8 10 12 14 16 18 200
1
2
3
4
5
6
7
8
SNR budget, , dB
CLB
in b
its p
er
tra
nsm
issi
on
fD
Ts = 0.01, N
r=8
fD
Ts = 0.01, N
r=4
fD
Ts = 0.11, N
r=8
fD
Ts = 0.11, N
r=4
Solid lines: using opt. parameters corresponding to SIMO boundDashed lines: using opt. parameters corresponding to SISO bound
![Page 47: 1 Designing Pilot-Symbol-Assisted Modulation (PSAM) Schemes for Time- Varying Fading Channels Tharaka Lamahewa Research School of Information Sciences.](https://reader037.fdocuments.in/reader037/viewer/2022110323/56649d7f5503460f94a62320/html5/thumbnails/47.jpg)
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Conclusions We considered the achievable information rates in
autoregressive fading channels with and without feedback under pilot-assisted channel estimation
Under realistic delays, feedback can provide some gain at low SNR and in moderately slow fading channels (fDTs = 0.01) and even at high SNR (compared to equal power allocation case)
In the relatively fast-fading case (fDTs = 0.1), use equal power allocation and just optimize the pilot spacing
By optimally designing the training parameters for SISO systems, the same parameters can be used to achieve near optimum capacity in both spatially i.i.d. and correlated SIMO systems.
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Current and Future Research What is the price of providing feedback in terms of
information rate loss in the reverse channel? How much power should we allocate for feedback transmission? Requires proper modelling and formulation.
So far, we have considered SISO and SIMO, extending the results to the MIMO
Model-based comparison of PSAM and superimposed training in terms of achievable information rates