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IEEE TRANSACTIONS ON COMMUNICATIONS, VOL. 49, NO. 5, MAY 2001 793
Interleaver Properties and Their Applications to theTrellis Complexity Analysis of Turbo Codes
Roberto Garello, Member, IEEE, Guido Montorsi, Member, IEEE, Sergio Benedetto, Fellow, IEEE, andGiovanni Cancellieri
AbstractIn the first part of this paper, the basic theory of in-terleavers is revisited in a semi-tutorial manner, and extended toencompass noncausal interleavers. The parameters that charac-terize the interleaver behavior (like delay, latency, and period) areclearly defined. The inputoutput interleaver code is introducedand its complexity studied. Connections among various interleaverparameters are explored. The classes of convolutionaland blockin-terleavers are considered, and their practical implementation dis-cussed. In the second part, the trellis complexity of turbo codes istied to the complexity of the constituent interleaver. A procedureof complexity reduction by coordinate permutation is presented,together with some examples of its application.
Index TermsConcatenated codes, interleavers, trellis com-plexity, turbo codes.
I. INTRODUCTION
I NTERLEAVERS are simple devices that permute (usuallybinary) sequences: they are widely used for improving errorcorrection capabilities of coding schemes over bursty channels.
Their basic theory has received a relatively limited attention in
the past, apart from some classical papers [1], [2]. Since the in-
troduction of turbo codes [3], where interleavers play a funda-
mental role, researchers have dedicated many efforts to inter-
leaver design. However, misunderstanding of basic interleaver
theory often causes confusion in the turbo code literature.In this paper, interleaver theory is revisited. Our intent is
twofold: first, we want to establish a clear mathematical frame-
work which encompasses old definitions and results on causal
interleavers. Second, we want to extend this theory to noncausal
interleavers, which can be useful for some application like, for
example, turbo codes.
We begin by a proper definition of the key quantities
that characterize an interleaver, like its minimum/maximum
delay, its characteristic latency, and its period. Then, interleaver
equivalence and deinterleavers are carefully studied. Interleaver
trellis complexity is analyzed by the introduction of a proper
input/output interleaver code. Connections between interleaver
Paper approved by M. Fossorier, the Editor for Coding and CommunicationTheory of the IEEE Communications Society. Manuscript received August 1,1997; revised July 6, 1999 and April 13, 2000. This work was supported in partby Qualcomm, Inc. and Agenzia Spaziale Italiana. This paper was presentedin part at the Sixth Communication Mini-Conference, Phoenix, AZ, November1997, and at the 2000 International Symposium on Information Theory, Sor-rento, Italy, June 2000.
R. Garello and G. Cancellieri are with the Dipartimento di Elettronica edAutomatica, Universit di Ancona, 60131 Ancona, Italy.
G. Montorsi and S. Benedetto are with the Dipartimento di Elettronica, Po-litecnico di Torino, 10129 Torino, Italy.
Publisher Item Identifier S 0090-6778(01)04090-9.
quantities are then explored, especially those concerning
latency, a key parameter for applications.
Finally, the class of convolutional interleavers is considered,
and their practical implementation discussed. Block inter-
leavers, which are the basis of most turbo code schemes, are
introduced as a special case.
A turbo code is obtained by the parallel concatenation of
simple constituent convolutional codes connected through an
interleaver. Turbo codes, although decoded through an iterative
suboptimum decoding algorithm, yield performance extremely
close to the Shannon limit [3]. In spite of the fact that severalresearch issues are still open, turbo codes are obtaining a large
success and their introduction in many international standards
is in progress. For decoding purposes, the trellises of the con-
stituent convolutional encoders are almost always terminated,
so that the turbo code can be considered as a block code.
Every linear block code can be represented by a minimal
trellis, which, in turn, can be used for soft-decision decoding
with the Viterbi or the BCJR [4] algorithms. For decoding pur-
poses, the complexity of a given trellis is usually expressed in
terms of complexity parameters like the maximum state com-
plexity (logarithm of the maximum number of states), the max-
imum branch complexity (logarithm of the maximum number
of branches), and the average branch symbol complexity (av-erage number of branch symbols per information bit). More-
over, fora given block code, itis well knownthatall com-
plexity measures strongly depend on the ordering of the time
axis, which in turn involves in principle all possible permuta-
tions of its segments.
It is a folk theorem among researchers in the field that
Maximum Likelihood decoding of turbo codes presents a
computational complexity increasing exponentially with the
interleaver length, so that it becomes prohibitively complex
when the turbo code employs a large interleaver, because of the
huge number of states involved. Thus, simpler, suboptimum
iterative decoding strategies have been proposed and suc-
cessfully applied. The previous, qualitative folk theorem maycontain a reasonable amount of truth. The trellis complexity of
turbo codes, however, has never been properly studied. In this
paper, it is analyzed and related to that of the constituent codes
and interleaver. By the introduction of the uniform interleaver,
the evaluation of the average complexity of a turbo code of a
given length can also be performed.
Strong connections exist between the true trellis com-
plexity parameters (minimized by coordinate permutation) and
the free distance of the code , that characterizes the
error probability performance at high signal-to-noise ratios. As
00906778/01$10.00 2001 IEEE
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GARELLO et al.: INTERLEAVER PROPERTIES AND THEIR APPLICATIONS TO THE TRELLIS COMPLEXITY ANALYSIS OF TURBO CODES 795
Fig. 1. Minimal trellises for the codes of (a) Example 1 and (b) Example 2.
Example 2: Given the code of Example 1, the following per-
mutation:
leads to . The gener-
ator matrix
has the LR property. It follows
We have .
The minimal trellis of is depicted in Fig. 1(b).
In general, the problem of finding the best permutation for
complexity minimization is NP-complete [25], [26].
D. Sectionalization
So far, we have considered an atomic representation of ,
i.e., a bit at every time . For clearness, in the fol-
lowing we will denote by , and , the complexity
parameters obtained when a sectionalization occurs such that agroup of bits corresponds to any time . The super-
script will be omitted only when obvious from the context.
As pointed out in [16], trellis sectionalization varies the state
and branchcomplexities,up topathological cases like .
When , the definition of the average branch symbol com-
plexity becomes
is not affected by sectionalization; moreover, it is
strictly tied to the computational complexity of the decoding
algorithms [22]. This suggests that is perhaps the mostappropriate parameter for complexity considerations. Optimal
sectionalization of the code trellis to reduce its complexity has
been studied in [29]. Several authors also allow for sectional-
ization into varying numbers of bits per trellis section, as
in [29].
III. INTERLEAVER THEORY: PAST WORK ON THE SUBJECT
The theory of interleavers was established in the two classical
papers [1] and [2]. In [1] causal interleavers were deeply ana-
lyzed: several definitions and results, equivalent to those pre-
sented in this paper, will be referred in the following. More-
over, many significant results on the spreading properties of in-terleavers (a subject that we have not considered in this paper)
and on their implementation were presented.
Other results were presented in [2] (see also [30]): Forney
invented periodic convolutional interleavers that are employed
in many applications and international standards.
Two considerations are important. First, classical interleaver
theory only concerned causal devices. As a consequence, some
quantities defined in our paper (like, for example, equivalence
classes of interleavers, or the interleaver code) were not strictly
necessary, and not introduced in [1] and [2]. Second, other re-
sults on causal interleavers were not explicitly presented in [1]
and [2], and are poorly documented or scattered elsewhere in
the literature.As a matter of fact, we think that most of the results on causal
interleavers presented in this paper are to be considered as a
re-interpretation of previous ones, even when an explicit refer-
ence is missing. Among the main contribution of this paper are
the general mathematical framework and all results concerning
noncausal interleavers, a subject which was not studied in the
past.
Recently, we partially presented our results in a preliminary
form in [31]. Similar definitions for causal interleavers can be
found in [32] together with some results about the interleaver
spread. Some other results concerning the cycle decomposition
of an interleaver and its implementation are presented in [33].
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796 IEEE TRANSACTIONS ON COMMUNICATIONS, VOL. 49, NO. 5, MAY 2001
Fig. 2. The delay function and some parameters of the interleaver of Example 3.
IV. INTERLEAVERS: BASIC DEFINITIONS
We begin to revisit interleaver theory by introducing some
basic definitions. They can be considered an extension of thedefinitions introduced in [1] for causal interleavers.
An interleaver is a device characterized by a fixed per-
mutation of the infinite time axis . maps bi-in-
finite input sequences into permuted
output sequences , with
. Although irrelevant for the interleaver proper-
ties, for simplicity we will assume in the following that is the
binary alphabet .
A. Delays and Period
We define the delay function as
The interleaver action can then be described as
We also define the following.
The maximum delay
The minimum delay
The characteristic latency
We say that is periodic with period , if there exists a
positive integer such that for all
i.e.,
In this paper, we will only consider periodic interleavers, be-
cause nonperiodic permutations are not used in practice. The
period is usually referred to, in the turbo code literature,
as the interleaver length or size, and is a crucial parameter in
determining the code performance. Often, it is also directly re-
lated to the latency introduced in the transmission chain; this
is not strictly correct, as we will see soon that the minimum
delay introduced by the interleaverdeinterleaver pair is instead
the characteristic latency . The ambiguity stems from the
common suboptimal implementation of a block interleaver (see
Section VII-B).
Example 3: Consider this interleaver and its action on the
binary sequences , as shown at the bottom of the page.
has period , minimum and maximum delay
, and characteristic latency .
Its delay function is depicted in Fig. 2.
In the following, we will describe an interleaver of period
only by its values in the fundamental interval
. For the interleaver of Example 3 we
have .
B. Interleaver Equivalence
Formal definition of equivalence classes of interleavers, notintroduced in classical theory, will prove useful in our frame-
work.
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GARELLO et al.: INTERLEAVER PROPERTIES AND THEIR APPLICATIONS TO THE TRELLIS COMPLEXITY ANALYSIS OF TURBO CODES 801
Fig. 5. Structure of a convolutional interleaver.
where is a finite basic permutation of length
,a nd is t he th e lement o f a shiftvector of elements
taking values in .
A visual implementation of the convolutional interleaver de-
scribed in (1) is shown in Fig. 5, where the reader can recognize
the similarities with the familiar structure of convolutional in-
terleavers described by Ramsey and Forney in [1] and [2]. The
input stream is permuted according to the basic permutation .The th output of the permutation register is sent to a delay line
with a delay , whose output is read and sent out. Notice
that in the realization of Fig. 5 the permutation is always non-
causal, except for the case of the identity permutation. As a con-
sequence, it is in general not physically realizable. In the next
subsection, we will describe a minimal realization of any peri-
odic causal interleaver.
Example 12: A simple class of interleavers stems from the
choice of the identity basic permutation
As an example, choosing , and
yields the equation shown at the bottom of the
page.
1) Implementation of Convolutional Interleavers with Min-
imal Memory Requirement: We have already proved in Corol-
lary 2 that the minimal memory requirement for the implemen-
tation of a causal interleaver is the constraint length , which
in turn is equal to the average of the delay profile. An important
property that relates the shift vector to the constraint length
of causal interleavers is given in the following lemma.
Lemma 5: The constraint length of a causal interleaver ofperiod is related to the shift vector through
Fig. 6. Minimal memory implementation of an interleaver.
Proof: For a causal interleaver, we proved in Corollary 3
that the average delay is equal to the constraint length, so that
From (1) we then have
In this section we describe an implementation with minimal
memory requirements of the encoder for a generic periodic
causal interleaver. The encoder is realized through a single
memory with size equal to the constraint length . The input
and output bits at a given time are read and stored with a single
Read-Modify-Write operation acting on a single memory cell
whose address is derived as follows (see Fig. 6).
At time we read from a memory cell, and write
into it. As a consequence, the successive contents of
that memory cell are
Thus, the permutation induces a partition
of the set of integers with the following equivalence relation-
ship:
and the constraint length is also the cardinality of this parti-
tion.
With the previous considerations in mind, we can devise the
following algorithm to compute the addresses to be used in
the minimal memory interleaver of Fig. 6.
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806 IEEE TRANSACTIONS ON COMMUNICATIONS, VOL. 49, NO. 5, MAY 2001
branch symbol complexity decreases from 253 625 branch sym-bols per information bits to 77 625 branch symbols per informa-tion bits.
Example 21: Consider a turbo code with the same con-
stituent convolutional encoders of Example 18, and rectangular
interleavers with different length , but equal column
number . Let us consider ,
and . In Fig. 10 we report the stateprofile of the two turbo codes, evaluated directly and through
the permutation . The result is striking: the two curves
obtained directly show a dependence of the maximum state
complexity on , and, in particular, a value of equal to
18 for and to 130 for . Instead, the two curves
obtained after applying yield a significant complexity
reduction, and, more important, a maximum state complexity
that is independent from , and given by . Using
the algorithm described in [37], we have computed the free
distance of the two turbo codes, and verified that it is also
independent from ; this suggests that a simple increase of
the interleaver length may not be beneficial, and, instead, that
the interleaver in a PCCC construction should be chosen aimingat maximizing the true trellis complexities parameters.
IX. CONCLUSION
In this paper, we have defined the main parameters that char-
acterize an interleaver, by extending classical concepts to non-
causal interleavers, too. After introducing the input/output in-
terleaver code, we have evaluated its complexity, and explored
the connections between the various parameters. We have then
focused on causal interleavers and on block interleavers, that are
both important for applications. These concepts have been ap-
plied to the evaluation of the trellis complexity of turbo codes.
We have also faced the problem of finding a time axis permuta-tion that reduces the complexity of turbo codes.
ACKNOWLEDGMENT
The authors wish to thank the Editor and the reviewers for
their valuable comments that helped to refocus and improve the
original manuscript. They are also grateful to F. Chiaraluce and
G. D. Forney, Jr., for their appropriate comments.
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[37] R. Garello, S. Benedetto, and P. Pierleoni, Computing the free distanceof turbo codes and serially concatenated codes with interleavers: Algo-rithms and applications, J. Select. Areas Commun., to be published.
Roberto Garello (M90) was born in Torino, Italy,on December 18, 1965. He received the Laurea inIngegneria Elettronicadegree (summa cum laude) in1990, and the Ph.D. degree in electronic engineeringin 1994, both from Politecnico di Torino.
In 1993, he spent six months visiting the Signaland Information Processing Laboratory, ETH,Zurich, Switzerland, and the Laboratory for Infor-mation and Decision Systems, MIT, Boston, MA.From October 1994 to August 1997, he was a DesignEngineer at Marconi Communications, Genova,
working on high-rate all-digital modems and signal processing applications.From September 1997 to September 1998, he was with the Dipartimento diElettronica of Politecnico di Torino working on the DSP implementation of aturbo decoder. Since November 1998, he has been an Associate Professor at theDipartimento di Elettronica ed Automatica of Universit di Ancona, Italy. Hismain interests include teaching, coding theory, and spread-spectrum systems.
Guido Montorsi (S93M95) was born in Turin,
Italy, on January 1, 1965. He received the Laureadegree in ingegneria elettronica in 1990 fromPolitecnico di Torino, Turin, Italy, with a mastersthesis concerning the study and design of codingschemes for HDTV, developed at the RAI ResearchCenter, Turin. In 1992, he spent the year as VisitingScholar in the Department of Electrical Engineeringat Rensselaer Polytechnic Institute, Troy, NY. In1994, he received the Ph.D. degree in telecommu-nications from the Dipartimento di Elettronica of
Politecnico di Torino.Since December 1997,he hasbeen an AssistantProfessor at thePolitecnicodi
Torino. His current interests include the area of channel coding, particularly onthe analysis and design of concatenated coding schemes and study of interativedecoding strategies.
Sergio Benedetto (SM90F97) received theLaurea in ingegneria elettronica (summa cum laude)from Politecnico di Torino, Italy, in 1969.
From 1970 to1979,he waswiththe Istituto di Elet-tronica e Telecomunicazioni, first as a Research En-gineer, then as an Associate Professor. In 1980, hewas made a Professor in Radio Communications atthe Universit di Bari. In 1981, he rejoined to Po-litecnico di Torino as a Professor of Data Transmis-
sion Theory in the Dipartimento di Elettronica. From1980 to 1981, he spent nine months at the SystemScience Department of University of California, Los Angeles, as a Visiting Pro-fessor, and three months at the University of Canterbury, New Zealand, as anErskine Fellow. He has co-authored two books in signal theory and probabilityand random variables (in Italian), and the books Digital Transmission Theory(Englewood Cliffs, NJ: Prentice-Hall, 1987) and Optical Fiber Communica-tions Systems (Boston, MA: Artech House, 1996), as well as about 200 papersfor leading engineering journals and conferences. Active in the field of digitaltransmission systems since 1970, his current interests are in the field of opticalfiber communications systems, performance evaluation and simulation of dig-ital communication systems, trellis-coded modulation and concatenated codingschemes.
Dr. Benedetto is currently the Area Editor for Signal Design, Modulation andDetection of the IEEE TRANSACTIONS ON COMMUNICATIONS.
Giovanni Cancellieri was born in Florence, Italy,in 1952. He graduated from the University ofBologna, Bologna, Italy, with a degree in electronicengineering and in physics.
He developed research in telecommunication sys-tems, with particular attention to networks and fibreoptics components. In 1980, he joined the Universityof Ancona, where he is currently Full Professor ofTelecommunications. He is co-author of more than100 papers and nine books. He is a consultant for theItalian Ministry of Research for funding projects of
advanced products and large enterprises.